referring now to the drawings , wherein like reference numerals refer to like components throughout , fig1 is broadly illustrative of a block diagram of a linear frequency modulated ( chirp ) laser radar system in accordance with the subject invention that includes a stable optical reference oscillator ( soro ) 10 which is used as a narrow bandwidth ( bw ) local oscillator and is comprised of a low power , cw source of coherent optical radiation which is used as a phase reference for a pair of optical transmit and deramp lasers 12 and 14 . a transmit signal consisting of a train of laser pulses , each having a respective random initial phase , is transmitted and received from a target , not shown , via a transmit / receive ( t / r ) optics subassembly 16 . a sample of the incoherent pulse signal from the transmit laser 12 is mixed , i . e . heterodyned , in an optical signal mixer 18 with the soro 10 providing an output of a phase difference signal corresponding to the phase difference between the two signals . this phase difference signal is fed to a narrow bandwidth transmit correction channel 20 including signal detector 22 , a signal sampler 24 , and an analog - to - digital ( a / d ) converter 26 so as to provide a digitized phase difference signal . the sampled digital phase difference signal is fed to a digital signal processor and data storage unit 28 for subsequent use as will be shown hereinafter in connection with fig4 where it will be compared against the phase of an ideal transmitted laser pulse . the received laser signal transmitted from transmit / receive ( t / r ) optics 16 is detected , as shown in fig1 , in a conventional heterodyne optical detector 30 . since the preferred embodiment of the invention is intended to use stretch signal processing of the return signals , a deramp laser signal is generated by the deramp laser 14 which is fed to the detector 30 where it is heterodyned with the return laser pulses . the output of detector 30 is fed to an a / d converter 32 in a main return channel 34 which feeds into the processor / data storage 28 . additionally , a portion of the deramp laser signal from the deramp laser 14 is fed to a second optical signal mixer 36 , which beats a portion of the soro signal with the deramp laser signal with a second phase difference signal being generated and fed into a narrow bandwidth deramp correction channel 38 , which also includes a detector 40 , a signal sampler 42 , and an a / d converter 44 similar to the transmit correction channel 20 . the second digitized phase difference signal which is also a digitized phase signal is also fed to the processor / data storage unit 28 for subsequent use as will be explained when fig4 is considered . referring now to fig2 which is intended to be further illustrative of the preferred embodiment of the subject invention shown in fig1 , in addition to the soro 10 , the transmit laser 12 , the receive deramp laser 14 , and the t / r optics 16 , a ramp signal generator 13 is connected to the transmit laser 12 . the frequency of transmit laser pulses is frequency modulated by a ramp ( chirp ) waveform 15 as shown in fig3 . with respect to the deramp laser 14 , it is driven by a separate ramp generator 17 which generates a waveform 19 as also shown in fig3 . fig2 also discloses that the detector 22 in the transmit correction channel 20 is comprised of a complex signal mixer having inphase ( i ) and quadrature ( o ) inputs . the same can be said of the detector 40 in the deramp correction channel 38 . it is significant to note also that the samplers 24 and 22 in fig2 provide an analog - to - digital conversion sampling rate which satisfies nyquist for error frequencies . accordingly , digital phase data simply are fed to the processor data storage 28 which is shown in fig2 coupled to a sar processing unit . fig2 also discloses that the transmit laser 12 is coupled to the transmit / receive optics 16 via a pulsed laser amplifier 21 . the heterodyne detector 30 shown in fig1 is shown in fig2 including a set of narrow band coherent receive detectors 48 which receive individual pulses included in the laser receive signal . the detected pulse signals are fed to a bandpass intermediate frequency ( if ) filter 50 whose output is then digitally converted by means of a narrow band a / d converter shown by reference numeral 32 . as in most , if not all radar systems , all operations are controlled by a master clock and synchronizer 52 . once samples of the digitized transmit correction phase signal , the deramp correction phase signal and the detected return signals are fed into the processor 28 , a sequence of events as shown in fig4 takes place . fig4 is intended to be merely illustrative of a functional sequence , while the apparatus used to implement these functions is shown in fig5 . in fig4 , reference numeral 54 is intended to denote a portion of the processor / data storage unit 28 shown in fig1 . reference numerals 56 , 58 and 60 denote three successive received return laser pulses . correction for the deramp signal 19 is applied first via a receive chirp correction from deramp correction channel 38 , because all of the errors caused by the deramp signal are consecutively lined up in time immediately after reception . transmit signal corrections are not yet ready for applications because the dramp process necessarily offsets the return signal slightly in time as shown by reference numerals 62 , 64 and 66 . this effect is overcome by a deskew operation in which a quadratic phase ( q ) is applied to the return pulses 62 , 64 and 66 , forcing them to become phase coherent as shown by reference numerals 68 , 70 and 72 . after the deskew operation , the transmit signal corrections are applied , resulting in if signals 74 , 76 and 78 . these signals are then fed to a range fast fourier transform ( fft ) unit in a conventional sar processor 46 for generating a display with appropriate azimuth motion compensation , autofocus , scan beam removal and azimuth fft operations being applied to the image signal data . referring now to fig5 , the components required for implementing a phase coherency is shown in a phase correction processor portion 79 of the processor / data storage unit 28 shown in fig2 . it is comprised of a deramp compensation functional element 80 , a first digital memory section 82 in which an “ ideal ” transmit pulse waveform is generated and stored , a complex ( i - q ) multiplier 84 , and a fft section 82 . these sub - assemblies provide a deramp signal correction signal providing such signals as shown by reference numerals 62 , 64 and 66 in fig4 while a transmit compensation functional element 88 , a second memory portion 92 , also used to store the waveform of an ideal transmit pulse , a complex multiplier 90 , and an inverse ifft 92 produce a transmit signal correction following the deramp corrected signals being fed to a complex multiplier 94 along with an output from the quadratic ( o ) phase generator 96 providing such signals as shown by reference numerals 68 , 70 and 72 in fig4 . fig6 is intended to illustrate that the deramp and transmit compensation units 80 and 88 shown in fig5 include a deskewing functional element 98 and a complex conjugate functional element 100 . these elements feed the i - q data from a / d converters 26 or 44 ( fig2 ) to a complex multiplier 102 where an “ ideal ” complex reference function of the ideal pulse waveform is applied either from the memory portion 82 or 90 , whereupon their complex components are fed into the complex multiplier 84 or the complex multiplier 90 as shown in fig5 . while coherence correction of the received laser signal is carried out in “ fast time ”, a correction of the linearity of the linear frequency modulation of the transmit laser pulse is carried out in “ slow ” time as will now be explained . as shown in fig7 , reference numeral 104 depicts an actual frequency variation 104 of the ramped frequency of laser pulses generated by the transmit laser 12 , which is inherently unstable in frequency to some extent and having a pulsewidth t , and a bandwidth b . a desired or ideal linear variation of the ramped frequency is shown by reference numeral 106 . linearity of the ramped frequency of the transmit pulse is achieved in slow time in a control loop as shown in fig8 by sampling one half of the digitized phase correction signal from a / d converter 26 over one - half the frequency bandwidth b / 2 . this portion of the signal is fed to a linearity correction unit 108 of the processor 28 , as shown in fig8 of the transmit correction channel 20 and which includes a digital tracking filter 110 connected to the a / d converter 26 , a polynomial generator consisting of a set of digital signal accumulators 112 1 . . . 112 n , and a digital / analog converter ( dac ) 114 . the accumulators couple their combined output into the dac 114 which couples a frequency corrective signal to the ramp generator 13 in the transmit correction channel 12 via signal lead 116 . thus , two separate and distinct functions are implemented in the subject invention , namely : ( 1 ) coherence is imparted to received laser signals generated by an incoherent transmit source ; and ( 2 ) a linearity correction function is supplied to the ramp generator 13 which controls the frequency of the transmitted pulses rom the t / r optics 16 . fig9 and 10 respectively illustrate the spectrum of the transmitted signal and the impulse response ( ipr ) of the received return signal . reference numeral 118 of fig9 depicts the spectrum of the transmitted laser signal , while reference numeral 120 represents the quadratic phase of the deskew operation . the deskew operation is shown off - centered at the peak of the quadratic phase term ; however , this is solved by providing a predistorted reference for a conventional 2d match filter used in the sar processor to generate a synthetic aperture image generated with the sar display shown in fig4 . reference numeral 122 of fig1 depicts the ipr before phase and linearity corrections have been made , while a solid line of waveform 124 depicts the ipr after the corrections are made and having a very high single main lobe and a set of side lobes of significantly reduced side lobes as opposed to the multiple main lobes in the ipr 122 . the modulation techniques utilized herein are not meant to be limited to single pulse linear fm stretch and linear fm chirp techniques , but are also applicable for pulse doublets , pulse triplets , pulse n - lets , non - linear fm , bi - phase coding , quadri - phase coding , n - phase coding , barker coding , frank coding , complementary coding and costas coding . having thus shown and described what is at present considered to be the preferred embodiment of the invention , it is to be noted that alterations and changes coming within the spirit and scope of the invention as set forth in the appended claims are herein meant to be included .