fig1 shows various signal curves illustrating the effect of an asymmetrical limiter upon a carrier frequency signal . these signal curves are plotted with respect to time t . an uninfluenced useful signal is marked a , a useful signal with a shifted zero axis , the broken straight line x 2 , is marked b , and a signal with an amplitude lower than that of the useful signal is marked c , which signal is also symmetrical about the axis x 2 . from the signal curve b , it can be seen how the positive and negative halfwaves of such a useful signal would be limited to different degrees if an incomplete limiter which causes a shift of the zero axis was present in the demodulation system . such a limiter would limit the signal symmetrically about the interrupted zero axis x 2 , but not symmetrically with respect to the actual uninterrupted zero axis x 1 . with such a limiting process , a limited useful signal would result which had the interrupted zero axis x . sub . 2 and , therefore , the zero passages of the signal about the axis x 1 would be shifted with respect to the zero passages of the uninfluenced useful signal a . the shift is such that the distances between the zero passages are reduced for the smaller halfwaves while they are increased for the other halfwaves . in previously known demodulation systems , such an influenced useful signal was fed , along its path , to a demodulator , for example a delay time demodulator , which used the spacing of the zero passages as a criterion for the demodulation . with an uninterfered with useful signal , i . e . a useful signal with no reduction in amplitude , the asymmetry of the limiter will hardly be noticed since the time shift of the zero passages is only slight due to the large , or steep , angle of intersection of the useful signal with respect to the zero axis . when the useful signal has a break - in , i . e . when the amplitude of the signal at the input of the limiter circuit drops considerably , however , this asymmetry will be much more significantly noticeable since there is now a much greater difference between the absolute values at the positive and negative halfwaves of the signal with respect to the unshifted zero axis . for an interference containing signal c , whose zero axis has been shifted in the same manner as that of the useful signal b , it can be clearly seen that the zero passages with respect to the axis x 1 are shifted to form alternatingly significantly shortened and lengthened spaces . this effect upon the spacing of the zero passages results in pairs of adjacent zero passages which lead to break - ins in the output signal especially when delay time modulators are used , i . e ., to an extreme falsification of the demodulated signal . the shift in the zero axis by the limiter and , consequently , the asymmetrical limiting of the signal and shift in its zero passages take place in synchronization with the occuring break - ins in the useful signal as a result of the undesired amplitude demodulation by the nonideal limiter . with the inclusion of the highpass filter in the signal path coupled to the output of the limiter , the shift of the zero passages is reversed in part in that the low frequency signal components produced from the asymmetrical limiting , inasmuch as they lie below the intended transmission range of the demodulation device , do not reach the demodulator . consequently with the inclusion of the highpass filter , the undesired modulation of the electron beam of the picture tube can be prevented . fig2 is a block circuit diagram of an embodiment of the present invention . the signal path of the useful signals begins in the transducer arrangement 1 marked as the information source , leads through a preamplifier 2 , which includes a lowpass filter for the higher harmonics of the transducer signal , as disclosed in u . s . pat . no . 3 , 691 , 317 , a highpass filter 3 , a limiter 4 and a highpass filter 5 according to the present invention ; from the highpass filter 5 , the signal goes through a frequency demodulator 6 and a video amplifier 7 to an electron beam tube 8 . details of blocks 1 to 4 and 6 to 8 are known from the video magnetic tape art . the highpass filter 5 according to the present invention may be constructed in accordance with the general knowledge in the filter art and is basically similar to the known highpass filter 3 . it is also possible for the transducer arrangement 1 to be a picture record pickup . this type of arrangement of a playback device is especially adaptable to being modified in accordance with the present invention . the waveform of the output signal of preamplifier 2 shown in fig3 represents a frequency modulated wave having a break - in lasting for a time corresponding to nearly three wavelengths . during this time waves of lower frequencies are superimposed on the useful signal of reduced amplitude . the superposition of waves of lower frequencies can be recognized by the varying shifting of the useful waves relative to the zero axis . at the output of the highpass filter 3 the superimposed waves of lower frequencies are eliminated as shown in fig4 . the result of the elimination is that the amplitudes of the waves during the break - in are nearly symmetrical to the zero axis . but another undesired effect is inserted now by the inevitable asymmetry of the limiter 4 which does not limit the waves of fig4 symmetrically to the zero axis but to the interrupted line . the effect is the limited waveform of fig5 being at the output of limiter 4 . this waveform has a new component of lower frequencies during the original break - in because the pulses of positive polarity are shorter than those of negative polarity . this new component according to the invention is eliminated by the highpass filter 5 , the output signal of which is shown in fig6 . here the third , the fourth and the fifth waves are elevated up to positive values in a manner that the integral with respect to time of the positive values of one wave is the same as the integral of the negative values of the same wave . thus especially a delay time demodulator is capable to produce a demodulated signal which does not differ too much from the signal which would appear if there were no break - in . but , moreover , by the elevation of the third to fifth wave in fig6 adjacent zero passages of the waves have nearly the same distance with respect to each other during the original break - in as they would have without any break - in ( though this is dependent on the relation of amplification and limitation level of the limiter ). thus also other demodulators produce a better signal during a break - in than without the highpass filter 5 . in fig7 the demodulated signal is shown as an example for the output signals of the demodulator 6 . a carrier frequency oscillation which has been , for example , frequency modulated with the video signal is picked up by the transducer arrangement . the deviation range of this modulated signal extends from 2 . 75 to 3 . 75 mhz , with the average gray value of the reproduced television picture corresponding to a frequency of 3 . 4 mhz . with such a carrier signal , the blocking ranges of the highpass filters 3 and 5 may extend to 400 khz if the video signal to be further processed has a bandwidth of about 3 mhz . if the blocking range of at least the highpass filter 5 is set at higher frequencies then interferences resulting from signal break - ins are even more effectively avoided ; the video signal bandwidth , however , is reduced when the above - mentioned deviation range is maintained . the less frequently such signal break - ins occur in the scanned signal , the easier it is to shift the limit of the blocking range toward lower frequencies . the preferred frequency demodulator is a known delay time demodulator or an improved demodulator as disclosed in the above - cited u . s . patent application to dickopp . in contrast to the uhf radio receivers previously discussed , the present invention utilizes the limiter in a playback device in which the transmission path has a transmission range with a relatively large ratio , only slightly less than 1 , of the absolute bandwidth ( e . g . 5 . 5 mhz ) to the maximum frequency of the transmission range ( e . g . 6 mhz ). in such a transmission path , a relatively large number of signal break - ins occur especially in comparison to such uhf receivers . these signal break - ins could cause the amplitude of the useful signal to be reduced by up to 100 % thereby causing heavy interference in the output signal of the limiter . since the limiters never operate completely symmetrically , these interferences in the signal will appear even stronger . such interferences which are produced by the so - called signal break - ins in the carrier frequency signal which still contain the desired useful information can be prevented by use of the additional highpass filter in the demodulation system in accordance with the present invention . it can be seen that the highpass filter of the present invention does not serve to attenuate low frequency noise , in contrast to the known resonant circuit in the anode circuit of a limiter tube discussed above ; rather this noise and other lower frequency interferences are already attenuated by the highpass filter 3 . highpass filter 5 , however , serves the purpose of preventing interferences caused by the signal break - ins which are amplified by the limiter . it will be understood that the above description of the present invention is susceptible to various modifications , changes and adaptations , and the same are intended to be comprehended within the meaning and range of equivalents of the appended claims .