fig1 is a diagram illustrating a data line sensing circuit 10 in accordance with an embodiment of the present invention . sensing circuit 10 includes a pmos sensing circuit 12 and an nmos sensing circuit 14 respectively connected between bit or data lines d 16 and d * 18 . the pmos sensing circuit 12 includes a first pmos transistor 20 including a source electrode connected to a sensing node 22 , a drain electrode connected to the data line d 16 and a gate electrode connected to the data line d * 18 , and a second pmos transistor 24 including a source electrode connected to the sensing node 22 , a drain electrode connected to the data line d * 18 and a gate electrode connected to the data line d 16 . the nmos sensing circuit 14 includes a first nmos transistor 26 with a drain electrode connected to a sensing node 28 , a source electrode connected to the data line d 16 and a gate electrode connected to the data line d * 18 , and a second nmos transistor 30 with a drain electrode connected to the sensing node 28 , a source electrode connected to the data line d * 18 and a gate electrode connected to the data line d 16 . a third pmos transistor 32 for supplying a power voltage vcc is connected to the sensing node 22 . a third nmos transistor 34 for supplying a ground voltage vss is connected to the sensing node 28 . a fourth nmos transistor 36 for supplying a negative bias voltage − vbb is connected to the sensing node 28 . p - sense control signal 38 is connected to the gate electrode of third pmos transistor 32 and n - sense ground control signal 40 is connected to the gate electrode of the third nmos transistor 34 while the n - sense below - ground control signal 42 is connected to the gate electrode of fourth nmos transistor 36 . if the third pmos transistor 32 and either the fourth nmos transistor 36 or the third nmos transistor 34 is turned on , the power voltage vcc and either the below - ground voltage − vbb or the ground voltage vss are supplied to the sensing nodes 22 and 28 , respectively , thereby operating the pmos sensing circuit 12 and the nmos sensing circuit 14 . in the present embodiment of the present invention , sensing circuit pull - up circuit 44 , including the pull - up third pmos transistor 32 and pull - up circuit control logic 46 , cooperatively function as the pull - up circuit to a cross - coupled sensing circuit 48 . similarly , nmos transistors 34 and 36 cooperatively function as a multistage pull - down circuit 50 as well as multistage pull - down circuit control logic 52 . fig2 illustrates a data line sensing circuit in accordance with another embodiment of the present invention . in the present embodiment , a data line sensing circuit 60 includes the cross - coupled sensing circuit 48 for sensing the state of data lines d 16 and d * 18 . to aid in the sensing process , the data line sensing circuit 60 further includes the pull - up circuit 44 which includes the third pmos transistor 32 controlled by the p - sense control signal 38 as generated by pull - up circuit control logic 46 . additionally , data line sensing circuit 60 further includes a multistage pull - down circuit 62 for providing a lower potential or voltage reference for pulling the sensing node 28 toward the provided lower voltage . in the present embodiment , the multistage pull - down circuit 62 includes a low vt nmos transistor 64 for reducing current leakage in the multistage pull - down circuit of the present embodiment . furthermore , the multistage pull - down circuit 62 further includes the nmos transistors 34 and 36 as well as a multistage pull - down circuit control logic 66 for generating n - sense latch control signal 68 , n - sense ground control signal 40 and n - sense below - ground control signal 42 . while a multistage pull - down circuit has been illustrated as including only two stages within the pull - down circuit , the present invention contemplates applications where waveforming of the pull - down potential profile would be desirable and , therefore , multiple stages beyond two pull - down transistors are contemplated within the scope of the present invention . fig3 is a waveform diagram illustrating the related signaling , in accordance with an embodiment of the present invention . in accordance with conventional memory device bit sensing , in an initial state , the data lines d 16 , d * 18 ( fig1 and 2 ) are precharged to an intermediate voltage of approximately ½ the level of vcc . the data lines are generally pass - gate coupled to the cross - coupled sensing circuit 48 ( fig1 and 2 ) with present data signals illustrated on data line d 16 and data line d * 18 . prior to the activation of either the pull - up circuit 44 or the multistage pull - down circuit 62 , a small differential signal is present on the respective data lines d 16 , d * 18 as illustrated in fig3 . once a sense enablement phase * control signal 70 becomes active low , the multistage pull - down circuit becomes activated . in the embodiment of fig2 , an n - sense latch control signal 68 is activated by the multistage pull - down circuit control logic 66 ( fig2 ), which provides current leakage protection to the cross - coupled sensing circuit 48 ( fig2 ). subsequently , the n - sense below - ground control signal 42 activates fourth nmos transistor 36 ( fig1 and 2 ) and pulls the cross - coupled sensing circuit 48 toward a voltage that is less than ground potential , thereby increasing the vgs across the transistors of the cross - coupled sensing circuit 48 to an amount greater than the vt of the transistors . by increasing the vgs across these transistors , the cross - coupled sensing circuit 48 is able to latch at a much faster rate . alternatively , it is also desirable to “ precharge ” the source electrode of transistor 64 by activating the n - sense below - ground control signal 42 just prior to the activation of transistor 64 . as illustrated in fig3 , once the n - sense below - ground control signal 42 becomes active , the data lines d 16 and d * 18 diverge at a much greater rate than occurs without utilization of a below - ground voltage , illustrated as the dashed waveform 18 ′. in order to prevent overly negative charging of the cross - coupled sensing circuit 48 and presenting deleterious conditions in a subsequent sense operation , once the separation has been accelerated , the cross - coupled sensing circuit 48 is coupled to a ground reference through activation of the n - sense ground control signal 40 . two separate control circuits are presented in fig4 and 6 for preventing the simultaneous activation of both the n - sense below - ground control signal 42 and the p - sense control signal 38 which would result in an undesirable reference voltage shift . fig4 illustrates a circuit having input signals of the sense enablement phase * control signal 70 and a p - sense activation status signal 72 which are combined through logic gates to prevent a simultaneous activation . fig5 illustrates the multistage pull - down waveform as generated by the circuit of fig4 and as observed at an n - sense activation status signal 74 . a time period 76 identifies the duration for activation of the n - sense below - ground control signal 42 and a time period 77 identifies a duration wherein both the n - sense ground control signal 40 and the p - sense control signal 38 may be activated . it should be appreciated that this duration is a function of the relative speeds and threshold voltages of the transistors of the cross - coupled sensing circuit 48 . it is desirable that the duration be adjusted to facilitate a more rapid separation of the differential signals while not retaining a negative potential for an extended duration after the pull - up circuit 44 becomes active . methods and circuits for implementing duty cycle adjustments to timing circuits are appreciated by those of ordinary skill in the art . fig4 further illustrates a logic gate 79 for coupling within the multistage pull - down circuit control logic 66 for eliminating the multistage ability of the multistage pull - down circuit 62 during testing , including probe testing . when probe test disable signal 81 is asserted , the sensing circuit 60 functions as a single - stage pull - down sensing circuit . such a sensing mode is desirable for lower - speed testing and segregation . disable signal 81 may also be used to configure sensing circuit 60 as a slower performing device . fig6 is a circuit diagram of a circuit for generating the n - sense below - ground control signal 42 , in accordance with another embodiment of the present invention . in fig6 , the sense enablement phase * control signal 70 couples to logic gates 78 , 80 , 82 and delay element 84 to form the n - sense ground control signal 40 and the n - sense below - ground control signal 42 . additionally , the delay element 84 is adjusted in conjunction with the logic to prevent the simultaneous assertion of both the n - sense below - ground control signal 42 and the p - sense control signal 38 . while the circuit of fig6 is illustrated as one embodiment of a pulse generator , other pulse generator embodiments are also contemplated which may form the desired waveform for the n - sense activation status signal 74 as illustrated in fig7 . fig7 illustrates the multistage pull - down waveform as generated by the circuit of fig6 and as observed at the n - sense activation status signal 74 . it should be noted that both the circuits of fig4 and 6 generate comparable waveforms , namely a time period 76 wherein the n - sense below - ground control signal 42 is activated and a time period 77 wherein both the n - sense ground control signal 40 and the p - sense control signal 38 may be activated , either simultaneously or in a staggered manner , which may be preferable for a particular semiconductor fabrication . as shown in fig8 , a semiconductor memory 90 includes an array 92 of memory cells 94 activated by word lines 96 fired by row driving circuitry 98 coupled to address buffers 100 and address decoders 102 . a plurality of data lines 104 communicates logic bits between the memory cells 94 and column selection and sensing circuitry 106 that includes sense amplifiers 108 . sense amplifiers 108 each include the sensing circuit 10 of the present invention and may further include precharge circuitry 110 and output circuitry 112 . in memory operations of the semiconductor memory 90 , the process of reading a logic bit from one of the memory cells 94 begins with the row driving circuitry 98 firing one of the active word lines 96 . while the word line 96 is propagating , the memory cells 94 connected to the active word line 96 fired by the row driving circuitry 98 activate and begin generating differential voltages on the data lines 104 representative of their stored logic bits . once these differential voltages are of sufficient magnitude to be sensed by the sense amplifiers 108 , the column selection and sensing circuitry 106 fires the sense amplifiers 108 , thus allowing the sense amplifiers 108 to sense the differential voltages on the data lines 104 . a selected one of the logic bits represented by one of the sensed differential voltages is subsequently provided to the output circuitry 112 for use by external circuitry ( not shown ). precharging of nodes within the sensing circuit may also be performed by precharge circuitry 110 prior to firing the sensing circuit 10 . as shown in fig9 , an electronic system 114 includes an input device 116 , an output device 118 , a processor device 120 , and a memory device 122 incorporating the semiconductor memory 90 of fig8 . as shown in fig1 , a semiconductor wafer 124 incorporates the semiconductor memory 90 of fig8 . although the present invention has been described with reference to particular embodiments , the invention is not limited to these described embodiments . rather , the invention is limited only by the appended claims , which include within their scope all equivalent devices or methods that operate according to the principles of the invention as described .