generally speaking , the invention features a coded saw device for automotive antitheft systems that is corrected for crosstalk and reflective signals . the device and detection circuitry is described in aforementioned u . s . patent application ser . no . 227 , 282 . for purposes of brevity , the teachings and description of the aforesaid application are incorporated herein by reference . referring now to fig1 there are shown a conventional steering wheel 10 and steering column 12 , as can be found in most motor vehicles and especially in automobiles . connected to an ignition switch 14 , hereinbelow described in greater detail , is a microprocessor 16 . many motor vehicles have electronic brains or computer processors such as that shown as reference numeral 16 , used to regulate the electrical , mechanical and chemical systems used in the vehicles . often , general purpose computers , a network thereof , or microprocessor - based electronic systems are used for the various functions . for example , a computer processor in an automobile may be used to regulate gas flow , to signal malfunctions in brake systems , to indicate the level of oil in the crankcase , to adjust internal temperature and the like . a collar housing 18 is shown mounted on the steering column 12 by means of screws 20 , although any suitable mounting means may be used for this purpose . the collar 18 houses a coupling coil or antenna , not shown , the use of which is explained hereafter . certain circuitry may also be contained within the collar 18 . referring now also to fig2 there is shown a perspective assembly view of the preferred embodiment of the present invention . the collar housing 18 has a circular aperture 19 cut therein . a printed circuit board or card 22 is housed by the collar housing 18 and encircles the ignition switch , not shown . the printed circuit board 22 has components mounted thereon that function as a receiver in cooperation with a saw device as hereinbelow described . encircling the printed circuit board aperture is a coupling coil 24 , the use of which is described in greater detail hereinbelow . an ignition key is shown generally at reference numeral 26 . the key 26 is adapted to be inserted through the collar aperture 19 and into the ignition switch , not shown . it should be noted that a conventional ignition key with a coded mechanical blade is not necessarily a requirement of the present invention . referring now also to fig3 there is shown a cross sectional side view of an ignition key 26 inserted into the ignition switch 14 . referring now also to fig4 there is shown a schematic representation of an ignition key 26 , the outline of which is shown in phantom . in the preferred embodiment , the key 26 has a longitudinal mechanical protuberance 28 , as do most conventional ignition keys . this longitudinal section 28 is preferably fabricated of metal and is mechanically coded to fit a particular ignition key lock , not shown . connected to the metal protuberance 28 is a key handle 30 . the handle 30 has an aperture 32 adapted to fit onto conventional key holders and key rings , not shown . the handle 30 can be rubber , plastic or any other suitable nonmetallic material . plastic is preferred . imbedded in the handle 30 is a surface acoustical wave ( saw ) device 34 . connected to the saw device 34 is a coupling coil or antenna 36 . the coil 36 forms a continuous loop connected to the saw device 34 at ports 38 and 40 and is disposed perpendicular to the major axis of the key 26 and the saw device 34 . also shown in fig4 is a second coupling coil or antenna 42 , which encircles the saw device coil 36 , but is not connected thereto . the second coil 42 is connected to a sensor , not shown , by means of an electrically conductive cable 44 . it can be seen that the key 26 and saw device coil 36 are adapted to move relative to the second coil 42 . referring now also to fig5 there is shown another cross sectional view of an ignition key in accordance with the present invention . in this embodiment , the saw device coil 36 is disposed parallel to the major plane of the key 26 and of the saw device 34 . this coil configuration can also be used with appropriate modification to the sensor coil 42 ( fig4 ). referring now also to fig6 there is shown a representation of a saw transponder , which is imbedded in an ignition key 26 and to which is connected a coupling coil 36 . it should be noted that other coil or antenna configurations , such as dipole antennas , can also be used . the transponder operates to convert a received signal to an acoustic wave and then to reconvert the acoustic energy back into an electrical signal for transmission via the coupling coil 36 . the signal transforming element of the transponder includes a substrate of piezoelectric material , not shown , on one surface of which is deposited a layer of metal , such as aluminum , forming a 6 - bit spatial pattern of electrodes or transducers shown in fig6 . in alternate embodiments , binary codes of more or less than six bits can be used . moreover , the code itself need not necessarily be binary . the piezoelectric substrate , not shown , is fabricated from yz lithium niobate ( linbo3 ). other materials can be used for the piezoelectric substrate , such as pzt ceramic and pvdf polymers . the aforementioned transducer pattern comprises two bus bars 62 and 64 connected to the coupling coil 36 . a leading transducer 50 and a plurality of coding elements or tap transducers 52 , 54 , 56 , 58 , 60 , 61 are also provided . these transducers are also known as interdigitated electrode arrays . the bus bars 62 and 64 define a path of travel , shown by arrow 66 , for an acoustic wave which is generated by the leading transducer 50 and propagates substantially linearly , reaching the tap transducers 52 - 61 , each in turn . the tap transducers 52 - 61 convert the acoustic wave back into electrical energy which is collected and therefore summed by the bus bars 62 and 64 . this electrical energy then activates the coupling coil 36 and is converted into electromagnetic radiation for transmission . in the preferred embodiment , the tap transducers 52 - 61 are provided at equally spaced intervals along the acoustic wave path 66 . an informational code associated with the transponder can be imparted by removing a selected number of tap transducers 52 - 61 . in alternate embodiments , delay pads , not shown , can be provided between tap transducers 52 - 61 . they can be made of the same material as , and deposited with , the bus bars 62 and 64 and the tap transducers 52 - 61 , each delay pad having a width sufficient to delay the propagation of the acoustic wave from one tap transducer 52 , for example , to the next 54 . a major problem that is encountered with the saw device described above is the existence of spurious signals . in the present context , the term spurious signal means unintended transponded signals that interfere with the correct interpretation . these spurious signal arise from two sources : ( 1 ) crosstalk and ( 2 ) double transit interference . referring to fig6 a simple explanation for the intended operation of the saw delay line is to imagine that an electrical excitation launches a saw from main idt 50 . this wave 66 travels towards a set of subidts 52 , 54 , 56 , 58 , 60 and 61 , each of which converts part of the saw energy back to electrical energy . however , since all idts are interconnected , all idts both launch and receive saws . crosstalk refers to output pulses created by launching and receiving saws within the subidt structure , e . g ., a saw launched by subidt 52 and received by subidt 60 . double transit interference refers to output pulses created by two saw transits . for example , a saw launched by main idt 50 and received by subidt 58 contributes to an output pulse ; this output pulse excites the coil antenna 36 as desired . however , acoustic energy is also reflected from subidt 54 , and redirected and picked up by subidts 56 , 54 and 52 as well as the main idt 50 . one may trace through a plethora of similar processes . cost and range considerations mandate the use of a reduced rf frequency , preferably below 50 mhz so that low cost electronic components developed for consumer electronics can be employed . cost considerations also dictate reducing the number of electronic components , for example , phase detectors . this mandates amplitude encoding for the saw device , for example using the presence of a pulse to indicate a binary 1 and its absence to indicate a binary 0 . such a coding scheme simplifies the detection and decoding electronics but introduces a higher vulnerability to spurious signals . two factors , described below , limit the number of code bits available in a low - frequency amplitude encoded system . 1 ) low frequency increases saw wavelengths , thereby increasing the required width for a subidt and limiting the number of subidts that can be incorporated on a reasonable size chip . for example , if the rf frequency is 44 . 3 mhz and the substrate is y cut z propagating lithium niobate , the saw wavelength is 77 microns . if 10 periods are reserved for each code bit , then a maximum of 10 idts could be arranged on a 1 cm chip , reserving 1 mm at each end for acoustic absorbing material . if 5 of the first code positions are left blank , leaving room for one main idt and 4 subidts in which to incorporate a code , as proposed by previous systems , this method permits 2 4 or 16 possible codes , which is barely enough for an antitheft system . 2 ) the equivalent circuit for a saw device is a capacitance in parallel with a resistance . it is well known to those skilled in the art of electronics that with a parallel capacitor - inductor - resistor circuit , the maximum response is obtained if the capacitance and inductance are in resonance ; that is , the capacitance c and inductance l should satisfy the relation : where f is the operating frequency . maintaining this equality for chips containing different codes requires that the number of idts on each chip be constant . in a phase - encoding method , this is automatic , since every bit is always &# 34 ; on &# 34 ;; only the phase is altered . in amplitude encoding , some bits , and therefore idts , are missing . each idt contributes to the overall saw device capacitance . maintaining constant capacitance therefore further limits the number of available codes . using the example given above , a 4 - bit code yields 16 distinct codes ; a 4 - bit code with the restriction that two bits are 1 &# 39 ; s and two bits are 0 &# 39 ; s yields only 6 distinct codes . this set of restrictions on frequency ( below 50 mhz ), chip size ( less than 1 cm chip length ), and coding method ( amplitude encoding ) appears to lead to an unreasonably low number of distinct codes , rendering the system ineffective . the invention disclosed herein breaks this barrier by providing means to reduce spurious signal levels so that the prior method for reducing spurious signals need not be applied . the invention requires that the first two bits be zeroes . this increases the number of code bits to 7 , yielding 2 7 or 128 distinct codes . there are 21 distinct codes with exactly 2 bits &# 34 ; on &# 34 ;; 35 codes with exactly 3 bits &# 34 ; on &# 34 ;, etc . these are enough codes for an effective antitheft system . however , this requirement necessitates a new method to reduce spurious signals . again referring to fig6 crosstalk originates from saw energy launched by one code subidt ( e . g ., that shown at reference numeral 52 ) and received by another subidt ( e . g ., 56 ). it is preferred that this type of process yield a much smaller output signal than the same process involving the main idt 50 and one subidt . one method for accomplishing this , is physically locating subidts in different acoustical channels . 2 this method is effective but limited . in this method up to eight &# 34 ; tap transducers &# 34 ; or subidts may be connected in series with acceptable spurious signal levels . this may be true for phase encoding but it is not true for amplitude encoding . when amplitude encoding is used and only the first two bits are zero , only one subidt can be used in each parallel acoustic track . the invention disclosed herein permits the use of two or more subidts per acoustic track , and / or allows a designer to dispense with separate acoustic tracks altogether . the invention accomplishes this by four distinct techniques : time narrowing weakens crosstalk signals relative to wanted code signals by using a narrower electrode width for the subidts than is used for the main idt . the wanted code signals then results from launching and receiving saws with one wide and one narrow idt ; unwanted spurious crosstalk signals result from two narrow idts and are therefore weaker . first consider fig7 a standard amplitude - coded delay line with no compensation for spurious signals . the delay line has a main transducer 50 and two subidts . subidt 52 is positioned to yield an output pulse in bit position 4 ; subidt 58 , in bit position 7 . ideally , the output would consist of pulses in bit positions 4 and 7 . in fact , because of crosstalk , there in an additional pulse in bit position 3 . the electrical pulse output of a device made according to fig7 is shown in fig8 . note that the crosstalk pulse in bit position 3 has the same strength as the wanted code pulses in bit positions 4 and 7 . now consider fig9 a time - narrowed coded saw delay line . note how in comparison to fig7 the subidts 112 and 114 , respectively , have narrower electrode widths compared to the launch idt 50 . fig1 presents the electrical pulse output of this device . note how this spurious crosstalk pulse in bit position 3 is narrower in time as well as weakened with respect to the wanted code pulses in bit positions 4 and 7 . although this method is illustrated for a simple code with only two code bits &# 34 ; on &# 34 ;, it is applicable to codes with more than two bits &# 34 ; on &# 34 ;. if the antitheft system designer requires a higher immunity to spurious signals , it is possible to employ a second technique call time shifting . it is well known to those skilled in the art of electronic digital communications that one preferred method to read bit - serial codes is to read the codes at the time corresponding to the expected center or peak of the code - bearing pulses . spurious signals occurring during the transition time in between pulses will have a far lower probability of interfering with reading the code , than spurious signals occurring during the center of the code - bearing pulses . it is possible to arrange for crosstalk spurious signals to occur during these transition times by adding a half code period or bit length x ( fig1 ) to the spacing between the main idt and the subidts . if the subidts spacing is m operating frequency wavelengths , then the centers of the wanted code - bearing pulses occur at times mt ( n + 1 / 2 ), where t is the operating frequency period and n is any integer . the spurious crosstalk pulses occur at times mt ( i ), where i denotes an integer . this is illustrated in fig1 , which presents the electrical pulse output of the device illustrated in fig1 . in comparing fig1 and 12 , note that in fig1 , the spurious crosstalk signal occurs at the center of bit 3 , while in fig1 it occurs in between bits 2 and 3 , thereby minimizing interference reading bits 2 and 3 correctly as binary zeroes . it has also been found useful to introduce a 90 -- phase shift between the spurious crosstalk signals and the wanted code - bearing signals to ensure that spurious signals are in quadrature with wanted signals . this prevents spurious signals from diminishing the amplitude of wanted code - bearing signals , helping to prevent falsely reading a binary one as a zero . while this technique has been illustrated for a two - subidt code , it is applicable to codes with a larger number of subidts . yet another technique to reduce crosstalk is to shape the pattern of electrode overlaps within the subidts to arrange that the crosstalk signals are spread over a longer period of time and to ensure that they are weaker than the wanted code - bearing signals . a method to accomplish this is shown in fig1 . subidts 102 and 104 have shaped electrode gap patterns . the shaping is arranged in opposite directions ( arrows a and b ) for the two subidts . this causes the crosstalk pulse arising from saws launched from subidt 102 and received by subidt 104 ( and vice versa ) to be spread out over approximately twice as much time as main code - bearing pulses launched from main idt 50 and received by subidts 102 and 104 ( and vice versa ). in addition , the crosstalk signals are weaker . this is illustrated by fig1 , which presents the electrical pulse output from a device fabricated in accordance with fig1 . note that the spurious crosstalk signal in bit position 3 is both spread out in time and weaker than the wanted code signals in bit positions 4 and 7 . the time - spreading principle illustrated in fig1 is applicable only when the number of subidts is limited to two , since a third subidt would have to be shaped like one of the original two subidts . the method is still applicable to more than two subidts if it is arranged that the spurious crosstalk occurs at times outside the range of code - bearing pulse arrival times . a fourth method for reducing spurious crosstalk signals is to add additional idts to the structure to generate additional signals of equal amplitude and time , and opposite phase , relative to the crosstalk signals . these additional signals then cancel the spurious signals . one way to arrange this is illustrated in fig1 . careful inspection of the figure will show that main idt 50 and subidts 106 and 108 will produce wanted pulses at bit positions 4 and 7 and a crosstalk pulse in bit position 3 . the interaction between additional idt 110 and main idt 50 produces a cancelling pulse in bit position 3 . this cancellation is illustrated in fig1 . there are many ways to produce this cancellation . for example , the main idt 50 could have been arranged to be confined to the same acoustic track width as the subidts and the cancellation could have been accomplished entirely with additional subidts . acoustic absorbing materials well known to those skilled in the art of saw devices could be applied to acoustically isolate the additional idts from the main code idts and each other . as stated above , double transit interference arises from the reflection of acoustic energy by an idt . methods to reduce double transit interference rely on reducing this acoustic reflection and employ impedance mis - matching . it may be shown that , for a convention bidirectional interdigital transducer , the difference between reflection loss l 11 and transduction loss l 13 is where g t is the equivalent circuit conductance of the idt , and g l is the load conductance , which includes both external load conductance and the conductance of other idts 3 , 4 . it is desired to arrange for l 11 to be as large as possible while minimizing increases in l 13 . in accordance with the above equation , this may be accomplished by increasing the ratio g l / g t . there are several ways to do this , including the following two . ( 1 ) connect an external resistor . this may be done either by directly wiring a resistor across the saw device or by terminating the pickup coil with a resistance . through the transforming action of the two coils , a resistance connected to either coil will contribute to load conductance . ( 2 ) connect additional idts to the bus bars , but ensure that they do not interact acoustically with the code - generating idts . this may be done either by placement or by covering the added idts with acoustic absorber . 1 . cole , p . h ., and vaughan , r . ( 1972 ), &# 34 ; electronic surveillance system &# 34 ;, u . s . pat . no . 3 , 706 , 094 . 2 . skeie , h ., ( 1986 ), &# 34 ; surface acoustic wave passive transponder having parallel acoustic paths &# 34 ;, u . s . pat . no . 4 , 620 , 191 . 3 . smith , w . r ., gerard , h . m ., collins , j . h ., reeder , t . m ., and shaw , h . j . ( 1969 ), &# 34 ; analysis of interdigital surface wave transducers by use of an equivalent circuit model &# 34 ;, ieee trans . mtt - 17 , pp . 856 - 864 . 4 . smith , w . r . ( 1973 ), &# 34 ; minimizing multiple transit echoes in surface wave devices ,&# 34 ; proc . 1973 ieee ultrasonic symposium , pp . 574 - 577 . since other modifications and changes varied to fit particular operating requirements and environments will be apparent to those skilled in the art , the invention is not considered limited to the example chosen for purposes of disclosure , and covers all changes and modifications which do not constitute departures from the true spirit and scope of this invention .