reference now is made in detail to the present preferred embodiments of the invention , examples of which are illustrated in the accompanying drawings , wherein like reference numerals indicate like elements throughout the several views . the invention disclosed in this patent is a novel approach to increasing data rate over a spread - spectrum system . the claimed invention may be manufactured , in whole or in part , as a digital signal processor ( dsp ), as an application specific integrated circuit ( asic ), from a general purpose processor , from discrete and / or analog electronic components , or as a combination of one or more of the dsp , asic , general purpose processor and discrete and / or analog components . the present invention broadly includes fec means , interleaver means , memory means , chip - encoder means , transmitter means , receiver means , spread - spectrum means , comparator means , chip - decoder means , deinterleaver means , and fec - decoder means . the interleaver means is coupled between the fec - encoder means and the memory means . the chip - encoder means is coupled between the memory means and the transmitter means . the transmitter means is coupled to the communications channel . the receiver means is coupled to the communications channel . the spread - spectrum means is coupled between the receiver means and the comparator means . the chip - decoder means is coupled between the comparator means and the deinterleaver means . the fec - decoder means is coupled to the deinterleaver means . the fec - encoder means encodes with an fec code , the data as fec data . fec data , as used herein , are the encoded data from any data source which are at the output of the fec - encoder means . the interleaver means interleaves the fec data as interleaved data . the memory means stores n bits of interleaved data as stored data . as used herein , stored data are the data stored in the memory means . n is the number of bits in a particular symbol . the chip - encoder means selects a chip - sequence signal , based on the n bits of stored data , from one of 2 n chip - sequence signals stored in the chip - encoder means . the selected chip - sequence signal is an output chip - sequence signal . in a preferred system , the 2 ′ chip - sequence signals are orthogonal and each chip - sequence signal has 2 n chips . alternatively , 2 n / 2 orthogonal chip - sequence signals can be selected and each chip - sequence signal can be sent as a positive or negative signal , creating bi - orthogonal signaling . the transmitter means translates the output chip - sequence signal to a carrier frequency and transmits the output chip - sequence signal at the carrier frequency as a radio wave over a communications channel , as a binary phase - shift - keyed ( bpsk ) or as a quaternary phase - shift - keyed ( qpsk ) spread - spectrum signal . the receiver means translates the spread - spectrum signal received to a processing frequency . because of the ease of digital processing , a preferred procedure is to translate , or down convert , the received spread - spectrum signal to baseband . the spread - spectrum means , for acquisition , multiplies the received spread - spectrum signal by a plurality of “ header ” chip - sequence signals . each header chip - sequence signal has an identical chip sequence . each header chip - sequence signal has a different delay from the other header chip - sequence signals . the preferred delay is one - half chip duration , although one chip duration is also workable . this accomplishes acquisition , by multiplying the received spread - spectrum signal by an identical chip - sequence signal , with different delays . the output of each multiplier is added forming a correlation , and the correlator with the largest output is selected . this approach permits the same 2 n correlators used for demodulation to be used for acquisition by changing the multiplying signals . a matched filter , however , could be used for acquisition , but using a matched filter would increase hardware . using a matched filter as a separate circuit for acquisition , which would be in addition to the embodiment disclosed herein , is well know in the art . after acquisition , the spread - spectrum means changes from multiplying by an identical “ header ” chip - sequence signal to multiplying by the 2 n different chip - sequence signals of the plurality of 2 n chip - sequence signals . accordingly , after acquisition , the received spread - spectrum signal is multiplied by each of the chip - sequence signals in the plurality of chip - sequence signals , with each chip - sequence signal in the plurality of chip - sequence signals having a different chip sequence from other chip - sequence signals from the plurality of chip - sequence signals . the outputs of each multiplier is added so that each multiplier - adder is a correlator . the comparator means selects the largest value at the output of the spread - spectrum means at each symbol time t s . the decoder means 36 decodes the largest value from the comparator means as an n - bit sequence or series of n - bits . the deinterleaver means deinterleaves the series of bits from chip - decoder means to deinterleaved data , and the fec - decoder means decodes the deinterleaved data as estimated data . the data , d ( t ), are fec encoded and interleaved , and successive n bits are stored . each n bit sequence is considered a symbol . for each n bits , one of 2 n orthogonal sequences is selected . each sequence has 2 n chips / symbol . each sequence is then amplitude modulation ( am ) modulated . thus the following signal is sent : k i ( t ) cos ω o t i = 1 , 2 , . . . , 2 n or k i  ( t )  cos   ω o  t   i = 1 , 2 , …  , 2 n or k i  ( t )  cos   ω o  t + h j  ( t )  sin   ω o  t   i = 1 , 2 , …  , 2 n 2  j = 1 , 2 , …  , 2 n 2 p i  ( t )  cos   ω o  t   i = 1 , 2 , …  , 2 n 2 or ± g i  ( t )  cos   ω o  t ± h j  ( t )  cos   ω o  t   i = 1 , 2 , …  , 2 n 4  j = 1 , 2 , …  , 2 n 4 where each waveform is orthogonal or bi - orthogonal to the others . in the receiver , 2 n correlators are used . if bi - orthogonal coding were used , then 2 n − 1 correlators are required . where f b is frequency ( bandwidth ) of bits , f c is frequency ( bandwidth ) of chips , and f 1 is frequency ( bandwidth ) of symbols . in the exemplary arrangement shown in fig3 - 6 , the improvement to the transmitter includes , by way of example , a forward - error - correction ( fec ) encoder 11 , interleaver 12 , and memory 13 . in fig3 and 4 , a chip - sequence encoder 14 is employed for selecting one of 2 n chip - sequence signals . the transmitter section , in fig3 and 4 , includes a product device 15 , a signal source 16 , and an antenna 17 . additional amplifiers and filters may be employed in the transmitter section , as is well known in the art . the interleaver 12 is coupled between the fec encoder 11 and the memory 13 . the chip - sequence encoder 14 is coupled between the memory 13 and the product device 15 . the signal source 16 is coupled to the product device 15 , and the antenna 17 is coupled to the product device 15 . the fec encoder 11 , of fig3 - 6 , encodes the data with an fec code . a convolutional encoder , concatenated coder comprising a convolutional and a reed solomon ( rs ) encoder , or other error - correcting codes can be used . the output of the fec encoder 11 is denoted herein as fec data . the interleaver 12 interleaves the fec data , using a bit interleaver algorithm as is well known in the art . the output of the interleaver 12 is denoted herein as interleaved data . the memory 13 stores n bits of data . the data may come from the interleaver 12 , and from other sources , such as signaling and other overhead data into the memory 13 . the data stored in the memory 13 is denoted herein as stored data . the number n represents the number of bits per symbol . the symbols are used or represented for a particular chip - sequence at the chip - sequence encoder 14 . referring to fig3 and 4 , the chip - sequence encoder 14 uses n bits of stored data for selecting a particular chip - sequence signal from a plurality of chip - sequence signals . the plurality of chip - sequence signals , in a preferred embodiment , includes 2 n orthogonal chip - sequence signals . the 2 n chip - sequence signals are stored in the chip - sequence encoder 14 . in response to the n bits of data stored each symbol time t s , one of the 2 n signals is outputted from the chip - sequence encoder 14 . the output of the chip - sequence encoder 14 is denoted herein as an output chip - sequence signal . in fig4 the output of the chip - sequence encoder 14 is multiplied by gate 115 with a plus or minus one , to generate a bi - orthogonal bpsk signal . referring to fig5 and 6 , the chip - sequence encoders 214 , 314 uses 2 n / 2 bits of stored data for selecting a particular chip - sequence signal from a plurality of chip - sequence signals . the plurality of chip - sequence signals , in a preferred embodiment , includes 2 n / 2 bi - orthogonal chip - sequence signals . the 2 n / 2 chip - sequence signals are stored in the chip - sequence encoders 214 , 314 . in response to the n bits of data stored each symbol time t s , one of the 2 n / 2 signals is outputted from the chip - sequence encoders 214 , 314 . the output of the chip - sequence encoder 214 is denoted herein as a quadrature - phase output chip - sequence signal , and the output from the chip - sequence encoder 314 is denoted herein as an inphase chip - sequence signal . the signal source 16 generates an in - phase carrier signal , and phase shifter 416 generates the quadrature - phase carrier signal , as is well known in the art . in fig6 the outputs of the chip - sequence encoders 214 , 314 are multiplied by multiplier devices 216 , 316 , respectively , by the quadrature - phase carrier signal and the in - phase carrier signal , and by gates 217 , 317 , respectively , with a plus or minus one , to generate a bi - orthogonal qpsk signal . the transmitter section translates the output chip - sequence signal to a carrier frequency , and transmits , as a radio wave , the output chip - sequence signal at the carrier frequency over a communications channel . the transmitted signal is a spread - spectrum signal . at the transmitter section in fig3 and 4 , the signal source 16 generates the signal for translating the output chip - sequence signal to the particular carrier frequency , and the product device 15 multiplies the output chip - sequence signal to the carrier frequency . the resulting product is the spread - spectrum signal which is radiated by the antenna 17 . for fig3 and 4 the product device 15 and signal source 16 are shown for an in - phase carrier . at the transmitter section in fig5 and 6 , the signal source 16 generates the signal for translating the output chip - sequence signal to the particular carrier frequency , and the product devices 216 , 316 multiplies the output chip - sequence signal to the carrier frequency . the phase - shift device 416 generates the quadrature component from the signal source 16 . the resulting product is the spread - spectrum signal which is radiated by the antenna 17 . note that in fig5 and 6 , a set of quadrature carriers , cos ω o t and sin ω o t , are generated in place of a simple in - phase carrier , of fig3 and 4 . [ 0063 ] fig7 shows how the basic receiver circuit , shown in fig2 is modified by the addition of a sequence detector that detects a symbol header . this decoder could be a simple matched filter which operates on the symbols . at the receiver , the receiver section translates the spread - spectrum signal to a processing frequency . the receiver section has an antenna 24 which is coupled to the communications channel , and a signal source 26 . the signal source 26 generates a signal which translates the received spread - spectrum signal by the mixer or product device 25 , to the processing frequency . in practice , as shown in fig8 two quadrature terms are obtained by multiplying by cos ω o t and sin ω o t and using standard receiver circuits . fig8 illustrates an in - phase device 25 and a quadrature - phase device 225 , coupled to a signal source 26 for cos ω o t and a signal source 226 for sin ω o t . alternatively , a single signal source and a phase shifter could be use to generate the cos ω o t and sin ω o t signals . in fig7 the plurality of product devices 21 , 22 , 23 are coupled to the product device 25 . the plurality of product devices 21 , 22 , 23 operates in cooperation with the chip - sequence - signal generator and controller 27 . for acquisition , a “ header ” chip - sequence signal is generated by the chip - sequence - signal generator and controller 27 . the header chip - sequence signal is generated as a plurality of header chip - sequence signals , with each chip - sequence signal in the plurality of header chip - sequence signals having a delay of one - half chip or one chip delay with respect to each other chip - sequence signal in the plurality of header chip - sequence signals . thus , each of the header chip - sequence signals in the plurality of header chip - sequence signals has an identical chip sequence as the first chip - sequence signal , but with a different delay . the plurality of product devices 21 , 22 , 23 multiplies the received spread - spectrum signal by the plurality of header chip - sequence signals , each with a respective , different delay . at the output of the plurality of product devices 21 , 22 , 23 , the plurality of integrators 31 , 32 , 33 integrates , respectively , a plurality of products from the plurality of product devices 21 , 22 , 23 . the products are integrated for a period of a header - chip - sequence signal . the quadrature detection embodiment of fig8 operates functionally equivalent to the in - phase embodiment described for fig7 with the addition of quadrature - phase products devices 221 , 222 , 223 and quadrature - phase integrators 231 , 232 , 233 . a set of a product device 21 and an integrator 31 , comprise a correlator , as is well known in the art . the comparator 35 selects a largest value from the plurality of integrators 31 , 32 , 33 , and for the quadrature - phase embodiment , of fig8 also from the plurality of integrators 31 , 32 , 33 , 231 , 232 , 233 . when the largest value is selected by the comparator 35 , a control signal is sent to the chip - sequence signal - generator and controller 27 , as to which of the particular paths from the plurality of product devices 21 , 22 , 23 and the respective plurality of integrators 31 , 32 , 33 has the largest value . the chip - sequence - signal generator and controller 27 locks onto the timing of the selected signal path . alternatively , a separate matched filter receiver could be used to detect the header and achieve synchronization . when the chip - sequence - signal generator and controller 27 are locked into the timing , the chip - sequence - signal generator and controller 27 generates a plurality of chip - sequence signals , with each chip - sequence signal different from the other chip - sequence signals in the plurality of chip - sequence signals and each being one of the 2 n , or 2 n / 2 , possible transmitted signals . thus , each chip - sequence signal from the chip - sequence - signal generator and controller 27 is different from the other chip - sequence signals in the plurality of chip - sequence signals , by having a different chip sequence from other chip - sequence signals . the plurality of chip - sequence signals are fed to the plurality of product devices 21 , 22 , 23 , in time synchronization with the received spread - spectrum signal , since acquisition has been achieved . acquisition is achieved by transmitting a prescribed number of chips to form the header . for example , if the desired signal - to - noise ratio ( snr ) at the correlator output for a single sequence were 20 db , and the snr of a chip were − 10 db , then a sequence of 1000 chips is adequate . in this case , assuming a chip rate of 4 megachips / second , the acquisition time t a =( 1000 / 4 ) microseconds = 250 microseconds . after acquisition , the plurality of product devices 21 , 22 , 23 , the chip - sequence - signal generator and controller 27 , and plurality of integrators 31 , 32 , 33 serve to demodulate which chip - sequence signal is embedded in the received spread - spectrum signal . the strongest signal path from the plurality of integrators 31 , 32 , 33 is selected by comparator 35 as the detected signal . upon detecting a particular chip - sequence signal from a particular path , the selected chip - sequence signal is decoded to n bits by chip decoder 36 . the de - interleaver 37 deinterleaves the interleaved n bits and the fec decoder decodes the deinterleaved data . an estimate of data is output from the fec decoder 38 . to ensure timing accuracy , the system could sample two or more times per chip . for data rates between 64 kb / s and 2 mb / s , technology permits sampling at four times the chip rate . however , at data rates of 100 mb / s and a chip rate of 400 mchips / s , one or two samples per chip appears to be the technological limit today . the present invention also includes a spread - spectrum method improvement for sending data over a communications channel , comprising the steps of storing , at a transmitter , n bits of interleaved data as stored data , with n a number of bits in a symbol , and selecting , at the transmitter in response to the n bits of stored data , a chip - sequence signal from a plurality of chip - sequence signals , as an output chip - sequence signal . the method then comprises the steps of transmitting the output chip - sequence signal as a radio wave , at a carrier frequency , over the communications channel , as a spread - spectrum signal and , translating , at a receiver , the spread - spectrum signal to a processing frequency as a received spread - spectrum signal . for acquisition , the received spread - spectrum signal is multiplied , at the processing frequency , by a header chip - sequence signal from the plurality of chip - sequence signals , with each chip - sequence signal having an identical chip sequence as the header chip - sequence signal , but with each chip - sequence signal having a delay of one - half or one chip , with each chip - sequence signal from the plurality of chip - sequence signals having a different delay from other chip - sequence signals . after acquisition , the received spread - spectrum signal is multiplied by the plurality of chip - sequence signals , with each chip - sequence signal from the plurality of 2 n chip - sequence signals having a different chip sequence from other chip - sequence signals in the plurality of chip - sequence signals , respectively . a plurality of products from the plurality of product devices are integrated during a period of a chip - sequence signal , and a largest value is selected from the plurality of integrators . the largest value from a respective integrator of the plurality of integrators is decoded into n bits of interleaved data . the invention preferably uses orthogonal or bi - orthogonal signaling to increase the processing gain . the result is a binary am signal ( bpsk ) or a qpsk signal and , therefore , the waveform is not degraded by amplifier nonlinearities . further , since only one waveform is sent and rake is employed in the receiver , multipath can be used to enhance performance . it will be apparent to those skilled in the art that various modifications can be made to the technique to acquire synchronization in high data rate cdma systems of the instant invention without departing from the scope or spirit of the invention , and it is intended that the present invention cover modifications and variations of the technique to acquire synchronization in high data rate cdma systems provided they come within the scope of the appended claims and their equivalents .