fig1 shows an example of a dars receiving circuit according to the present invention , in which a portion 30 surrounded by a one - dot chain line is formed into a one - chip ic . signals a 1 to a 3 , and b 1 to b 3 are received by an antenna 51 , and the received signals a 1 to b 3 are supplied to mixer circuits 32 i and 32 q via a band - pass filter 52 , which is formed of , for example , an saw filter and which has a passing bandwidth of 12 . 5 mhz and furthermore via a high - frequency amplifier 31 . in a local oscillation circuit 33 , as shown in fig2 a , an oscillation signal slo having a frequency equal to the center frequency fc between the signal a 3 and the signal b 3 is formed , this signal slo is supplied to a phase processing circuit 34 , whereby two local oscillation signals sli and slq , whose phases differ by 90 ° from each other , with the frequency being kept at the value fc , are formed , and these signals sli and slq are supplied to the mixer circuits 32 i and 32 q , respectively . in the following description , for brevity of explanation , it is assumed that , as shown in fig2 a , the signal sa represents each of the signals a 1 to a 3 , and the signal sb represents each of the signals b 1 to b 3 . that is , it is assumed that sa = a 1 , sa = a 2 , or sa = a 3 , and that sb = b 1 , sb = b 2 , or sb = b 3 . then , it is arranged that : where ea is the amplitude of the signal sa , eb is the amplitude of the signal sb , ωa is the angular frequency of the signal sa , and ωb is the angular frequency of the signal sb . where el is the amplitude of the signals sli and slq , and ωc = 2πfc . then , from the mixer circuits 32 i and 32 q , signals sifi and sifq as described below are extracted : sifi = ( sa + sb ) × sli ⁢ ⁢ = ea · sin ⁢ ⁢ ω ⁢ ⁢ at × el · sin ⁢ ⁢ ω ⁢ ⁢ ct + eb · sin ⁢ ⁢ ω ⁢ ⁢ bt × el · sin ⁢ ⁢ ω ⁢ ⁢ ct ⁢ ⁢ = α ⁢ { cos ⁡ ( ω ⁢ ⁢ a - ω ⁢ ⁢ c ) ⁢ t - cos ⁡ ( ω ⁢ ⁢ a + ω ⁢ ⁢ c ) ⁢ t } + β ⁢ { cos ⁡ ( ω ⁢ ⁢ b - ω ⁢ ⁢ c ) ⁢ t - ⁢ ⁢ cos ⁡ ( ω ⁢ ⁢ b + ω ⁢ ⁢ c ) ⁢ t } sifq = ( sa + sb ) × slq ⁢ ⁢ = ea · sin ⁢ ⁢ ω ⁢ ⁢ at × el · cos ⁢ ⁢ ω ⁢ ⁢ ct + eb · sin ⁢ ⁢ ω ⁢ ⁢ bt × el · cos ⁢ ⁢ ω ⁢ ⁢ ct ⁢ ⁢ = α ⁢ { sin ⁡ ( ω ⁢ ⁢ a + ω ⁢ ⁢ c ) ⁢ t + sin ⁡ ( ω ⁢ ⁢ a - ω ⁢ ⁢ c ) ⁢ t } + β ⁢ { sin ⁡ ( ω ⁢ ⁢ b + ω ⁢ ⁢ c ) ⁢ t + ⁢ ⁢ sin ⁡ ( ω ⁢ ⁢ b - ω ⁢ ⁢ c ) ⁢ t } as will be described later , of the signals sifi and sifq , the signal components of angular frequencies ( ωa − ωc ) and ( ωb − ωc ) are used as the intermediate frequency signals , and the signal components of angular frequencies ( ωa + ωc ) and ( ωb + ωc ) are removed by the intermediate frequency filter . therefore , for the sake of simplicity , if the signal components of angular frequencies ( ωa + ωc ) and ( ωb + ωc ) to be removed are ignored , the above equations become : here , if it is arranged that ωa = ωc − δω with regard to the signal sa , since , as is also shown in fig2 a , the signal sa and the signal sb are symmetrically distributed about the frequency fc , the following equation holds : then , if these equations are substituted in the equations for the signals sifi and sifq , the following equations are obtained : sifi = α · cos ⁡ ( ω ⁢ ⁢ c - δ ⁢ ⁢ ω - ω ⁢ ⁢ c ) ⁢ t + β · cos ⁡ ( ω ⁢ ⁢ c + δ ⁢ ⁢ ω - ω ⁢ ⁢ c ) ⁢ t ⁢ ⁢ = α · cos ⁡ ( - δ ⁢ ⁢ ω ) ⁢ t + β · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t ⁢ ⁢ = α · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t + β · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t sifq = α · sin ⁡ ( ω ⁢ ⁢ c - δ ⁢ ⁢ ω - ω ⁢ ⁢ c ) ⁢ t + β · sin ⁡ ( ω ⁢ ⁢ c + δ ⁢ ⁢ ω - ω ⁢ ⁢ c ) ⁢ t ⁢ ⁢ = α · sin ⁡ ( - δ ⁢ ⁢ ω ) ⁢ t + β · sin ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t ⁢ ⁢ = - α · sin ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t + β · sin ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t these signals sifi and sifq are then supplied to phase - shift circuits 35 i and 35 q . the phase - shift circuits 35 i and 35 q are formed by an active filter in which , for example , a capacitor , a resistor , and an operational amplifier are used . the phase - shift circuit 35 i phase - shifts the signal sifi by a value φ ( φ is an arbitrary value ), and the phase - shift circuit 35 q phase - shifts the signal sifq by a value ( φ + 90 °). in this manner , the phase - shift circuits 35 i and 35 q cause the signal sifq to lead the signal sifi by 90 °, and the following equations hold : sifi = α · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t + β · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t sifq = - α · sin ⁡ ( δ ⁢ ⁢ ω ⁢ ⁢ t + 90 ⁢ ° ) + β · sin ⁡ ( δ ⁢ ⁢ ω ⁢ ⁢ t + 90 ⁢ ° ) ⁢ ⁢ = - α · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t + β · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t therefore , between the signal sifi and the signal sifq , the signal components α · cos δωt are at the opposite phase from each other , and the signal components β · cos δωt are in phase . these signals sifi and sifq are then supplied to an addition / subtraction circuit 36 , and a control signal ssw is supplied from a terminal 37 to the addition / subtraction circuit 36 . this control signal ssw controls the operation of the addition / subtraction circuit 36 in such a way that when the program of the ensemble a is to be listened to , the addition / subtraction circuit 36 acts as a subtraction circuit , and when the program of the ensemble b is to be listened to , the addition / subtraction circuit 36 acts as an addition circuit . therefore , a signal sif such as that described below is extracted from the addition / subtraction circuit 36 in such a manner as to correspond to the control signal ssw . that is , during subtraction , the following is extracted : ⁢ = 2 ⁢ α · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t ⁢ ⁢ = el · ea · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t , ⁢ = 2 ⁢ β · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t ⁢ ⁢ = el · eb · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t here , the signal sif = el · ea · cos δωt which is obtained during subtraction is , as is also shown in fig2 b , the same intermediate frequency signal when the signal sa is received . the signals sif 1 to sif 3 contained in this signal sif are the intermediate frequency signals of the signals a 1 to a 3 . also , the signal sif = el · eb cos δωt which is obtained during addition is , as is also shown in fig2 c , the same intermediate frequency signal when the signal sb is received . the signals sif 1 to sif 3 contained in this signal sif are the intermediate frequency signals of the signals b 1 to b 3 . therefore , this signal sif is supplied to a band - pass filter 41 h for an intermediate - frequency filter having passing characteristics such as those indicated by the broken line in , for example , fig2 b and 2c , whereby an intermediate frequency signal sif 3 of a terrestrial - wave signal a 3 or b 3 is extracted . at this time , the intermediate frequency signals sif 1 and sif 2 and the above - mentioned signal components of angular frequencies ( ωa + ωc ) and ( ωb + ωc ) are removed by the band - pass filter 41 h . then , this intermediate frequency signal sif 3 is supplied to a demodulation circuit 43 h via a variable gain amplifier 42 h for agc , whereby a digital audio signal of the target program is demodulated , and this signal is supplied to a selecting / combining circuit 44 . also , the signal sif from the addition / subtraction circuit 36 is supplied to a band - pass filter 41 l for an intermediate - frequency filter having passing characteristics such as those indicated by the broken line in , for example , fig2 b and 2c , whereby intermediate frequency signals sif 2 and sif 1 of the satellite - wave signals a 1 and a 2 , or b 1 and b 2 are extracted . at this time , the intermediate frequency signal sif 3 and the above - mentioned signal components of angular frequencies ( ωa + ωc ) and ( ωb + ωc ) are removed by the filter 41 l . then , these intermediate frequency signals sif 2 and sif 1 are supplied to a demodulation circuit 43 l via a variable gain amplifier 42 l for agc , whereby a digital audio signal of the target program is demodulated , and this signal is supplied to the selecting / combining circuit 44 . then , in the selecting / combining circuit 44 , the digital signal from the demodulation circuit 43 h and the digital signal from the demodulation circuit 43 l are selected or combined according to the received status of the signals a 1 to b 3 , and is extracted at an output terminal 45 . of course , when it is desired to give priority to a receiving environment of a mobile unit in which the receiver is mounted and to satellite - wave reception , the agc voltage obtained from the level detection circuit 46 l may be supplied as a gain control signal . at this time , parts of the intermediate frequency signals from the demodulation circuits 43 h and 43 l are supplied to level detection circuits 46 h and 46 l , whereby agc voltages are formed , and these agc voltages are supplied , as gain control signals , to the amplifiers 42 h and 42 l , whereby agc is performed . in addition , although the level variation of the satellite wave is relatively small , the level variation of the terrestrial wave is relatively large . therefore , for the high - frequency amplifier 31 , a variable gain amplifier is used , and the agc voltage obtained from the level detection circuit 46 h is supplied , as a gain control signal , to the amplifier 31 , whereby agc is performed . in this manner , according to the receiving circuit of fig1 , a broadcast by dars can be received , and in a case where the ensemble is switched between the ensemble a and the ensemble b , the frequency fc of the local oscillation signals sli and slq does not need to be changed . consequently , the local oscillation circuit 33 may be formed in a standard construction and does not become complex . also , since the phase noise characteristics of the local oscillation signals sli and slq are not decreased , the error rate of the digital signal does not become worse . in addition , when the ensemble is to be switched , the addition / subtraction circuit 36 need only be switched to an addition operation or a subtraction operation . consequently , the switching can be performed at high speed , and the problem of not being able to receive the ensemble during switching time does not occur . as is also clear from fig2 b and 2c , since the upper - limit frequency of the occupied bandwidth of the intermediate frequency signal sif is equal to a half of the bandwidth of one ensemble , and the center frequencies of the filters 41 h and 41 l become approximately 1 . 3 mhz and 4 . 4 mhz , it is possible to form each of the filters 41 h and 41 l by an active filter . therefore , it is possible to form the entirety into a one - chip ic as an ic 30 , excluding a band - pass filter 52 at the antenna input stage , and this is effective in reducing the costs and the size of the receiver . in addition , since the intermediate frequency of the intermediate frequency signals sif 3 to sif 1 is as low as several mhz , even when the demodulation of the demodulation circuits 43 h and 43 l is performed by a digital process , as shown in , for example , fig1 , for the receiving method , a single conversion may be used , the construction becomes simple , and the number of parts is decreased . in the receiving circuit shown in fig3 , a case is shown in which , by inverting or non - inverting the phase of the local oscillation signal slq when the ensemble a is received and when the ensemble b is received , the signals sifi and sifq are always added together . more specifically , in the receiving circuit in fig3 , the control signal ssw is supplied as a phase control signal to the phase processing circuit 34 , so that the phase of the local oscillation signal slq is controlled such that : slq =+ el · cos ω ct . . . when the ensemble b is received , slq =− el · cos ω ct . . . when the ensemble a is received . the phase of the local oscillation signal sli is fixed , as described above : in place of the addition / subtraction circuit 36 in fig1 , an addition circuit 38 is provided , and the signals sifi and sifq output from the phase - shift circuits 35 i and 35 q are supplied to the addition circuit 38 . according to such a construction , in the case of slq =+ el · cos ωct , in the addition circuit 38 , the signal sifi and the signal sifq are added together . therefore , as is described with reference to the receiving circuit of fig1 , the signal sif extracted from the addition circuit 38 becomes as follows : ⁢ = el · eb · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t therefore , it is possible to listen to the program of the ensemble b . on the other hand , in the case of slq =− el · cos ωct , the output signal of the phase - shift circuit 35 q becomes the signal − sifq . therefore , since , in the addition circuit 38 , subtraction between the signal sifi and the signal sifq is performed , as is described with reference to the receiving circuit of fig1 , the signal sif extracted from the addition circuit 38 becomes : ⁢ = el · ea · cos ⁢ ⁢ δ ⁢ ⁢ ω ⁢ ⁢ t therefore , it is possible to listen to the program of the ensemble a . in this way , also in the receiving circuit of fig3 , a dars broadcast can be received . in particular , according to the receiving circuit of fig3 , in a case where the ensemble is switched between the ensemble a and the ensemble b , it is only necessary to invert or non - invert the phase of the local oscillation signal slq by the phase processing circuit 34 . therefore , the ensemble can be switched quickly . also , since the phase - shift circuits 35 i and 35 q and the addition circuit 38 can be formed by a poly - phase filter , the phase characteristics of the signal sifi and the signal ± sifq can be improved . in fig4 , a case is shown in which the phase of the intermediate frequency signal sifi is constant regardless of the ensemble which is received , but the phase of the intermediate frequency signal sifq is inverted or non - inverted between when the ensemble a is to be received and when the ensemble b is to be received . more specifically , the mixer circuit 32 q is formed as a double balanced - type by transistors q 321 to q 327 . the received signals a 1 to a 3 and b 1 to b 3 are extracted as a balanced type from the amplifier 31 and are supplied to transistors q 322 and q 323 . furthermore , the local oscillation signal slq is extracted as a balanced type from the phase processing circuit 34 and is supplied to transistors q 324 , q 327 , q 325 , and q 326 . consequently , the intermediate frequency signal sifq is extracted as a balanced type from the mixer circuit 32 q . that is , for example , the intermediate frequency signal + sifq is extracted from the transistors q 324 and q 326 , and the intermediate frequency signal − sifq is extracted from the transistors q 325 and q 327 . then , these intermediate frequency signal ± sifq are supplied to a switching circuit 39 . this switching circuit 39 is formed as a balanced type by transistors q 391 to q 397 , and the intermediate frequency signals ± sifq which are supplied thereto are supplied to a phase - shift circuit 36 q in accordance with the control signal ssw with the phase kept as it is or with the phase being inverted . more specifically , based on the control signal ssw , when the transistor q 395 is on and transistor q 396 is off , the transistors q 392 and q 393 are turned on , and the transistors q 391 and q 394 are turned off . therefore , the intermediate frequency signal + sifq extracted from the transistors q 324 and q 326 is supplied to one of the balance input terminals of the phase - shift circuit 36 q via the transistor q 392 . also , the intermediate frequency signal − sifq extracted from the transistors q 325 and q 327 is supplied to the other one of the balance input terminals of the phase - shift circuit 36 q via the transistor q 393 . however , based on the control signal ssw , when the transistor q 396 is on and the transistor q 395 is off , the transistors q 391 and q 394 are turned on , and the transistors q 392 and q 393 are turned off . therefore , the intermediate frequency signal + sifq extracted from the transistors q 324 and q 326 is supplied to the other one of the balance input terminals of the phase - shift circuit 36 q via the transistor q 391 . also , the intermediate frequency signal − sifq extracted from the transistors q 325 and q 327 is supplied to one of the balance input terminals of the phase - shift circuit 36 q via the transistor q 394 . therefore , since the phase of the intermediate frequency signal sifq supplied to the phase - shift circuit 36 q is inverted or non - inverted in accordance with the control signal ssw , the intermediate frequency signal sif of the ensemble a or the ensemble b is output from the addition circuit 38 . in this case , since the phase of the intermediate frequency signal sifq need only be inverted or non - inverted by the switching circuit 39 , it is possible to quickly switch the ensemble . although the phase of the intermediate frequency signal sifi is kept fixed , the intermediate frequency signal sifi output from the mixer circuit 32 i may be supplied to a phase - shift circuit 36 i via a switching circuit having the same construction as that of the switching circuit 39 , and the switching . circuit may be kept fixed . fig5 shows a circuit 34 q of a portion which switches the phase of the local oscillation signal slq within the phase processing circuit 34 in fig3 . that is , the mixer circuit 32 q is formed as a double balance - type as described in fig4 , and the received signals a 1 to a 3 and b 1 to b 3 are extracted as a balanced type and are supplied to the transistors q 322 and q 323 . furthermore , the switching circuit 34 q is formed as a double balanced - type by the transistors q 341 to q 347 . the local oscillation signal + slq of one of the phases is supplied to the transistors q 345 and q 346 , and the local oscillation signal − slq of the other phases is supplied to the transistors q 344 and q 347 . also , the balanced - type control signal ssw is supplied to the transistors q 342 and q 343 . then , based on the control signal ssw , when the transistor q 342 is on and the transistor q 343 is off , the transistors q 344 and q 345 are turned on , and the transistors q 346 and q 347 are turned off . therefore , the local oscillation signal + slq is supplied to the transistors q 324 to q 327 via the transistor q 345 and further via the emitter - follower transistor q 349 . also , the local oscillation signal − slq is supplied to the transistors q 325 and q 326 via the transistor q 344 and further via the emitter - follower transistor q 348 . however , based on the control signal ssw , when the transistor q 343 is on and the transistor q 342 is off , the transistors q 346 and q 347 are turned on , and the transistors q 344 and q 345 are turned off . therefore , the local oscillation signal + slq is supplied to the transistors q 325 and q 326 via the transistor q 346 and further via the transistor q 348 . also , the local oscillation signal − slq is supplied to the transistors q 324 and q 327 via the transistor q 347 and further via the transistor q 349 . therefore , since the phase of the local oscillation signal slq supplied to the mixer circuit 32 q is made to lead or reversed in accordance with the control signal ssw , the intermediate frequency signal sif of the ensemble a or the ensemble b is output from the addition circuit 38 . also in this case , since the phase of the local oscillation signal slq need only be inverted or non - inverted by the switching circuit 34 q , the ensemble can be switched quickly . many different embodiments of the present invention may be constructed without departing from the spirit and scope of the present invention . it should be understood that the present invention is not limited to the specific embodiments described in this specification . to the contrary , the present invention is intended to cover various modifications and equivalent arrangements included within the spirit and scope of the invention as hereafter claimed . the scope of the following claims is to be accorded the broadest interpretation so as to encompass all such modifications , equivalent structures and functions .