Noise eliminator for television synchronizing signal separating circuits
It is therefore an object of the present invention to provide a circuit for use in sync separator circuits to decrease the length of time required to recover from negative voltage spikes on the input composite video signal. 
     The foregoing and numerous other objects and advantages of the present invention will become apparent as the same is more fully understood from the following description and drawings which describe the preferred embodiment of the invention. It is to be understood, however, that this emobodiment is not intended to be exhausting nor limiting of the invention but is given for purposes of illustration. 
    
    
     BRIEF DESCRIPTION OF THE DRAWING 
     In the drawing: 
     FIG. 1 is a block diagram of a sync separator according to the present invention; and 
     FIG. 2 is a schematic diagram of one embodiment of the present invention. 
    
    
     DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
     Referring now to FIG. 1, therein is shown a block diagram of a sync separator circuit including the present invention. 
     The composite video signal enters the sync separator circuit on input line 10 and the separated sync signal exits the circuit on output line 12. The composite video signal is first coupled to dc restorer 2. The output of dc restorer 2 is one input to amplitude separator 4 the other input thereto is a reference voltage on line 16. The output of amplitude separator 4 is connected to output line 12 and also to monostable multivibrator 8 whose output terminal is connected to variable current source 6. Current source 6 supplies the current for the dc restoration function accomplished by dc restorer 2. 
     For accurate separation of the sync pulses from the incoming composite video signal, it must be dc restored, otherwise changes in the average picture level (APL) may cause the video signal to be clipped above the blanking level. DC restoration is performed by dc restorer 2 which may be of any conventional design. This dc restoration is accomplished by clamping the tip of the sync signal to a predetermined dc level, usually ground. The clamped video signal is coupled to amplitude separator 4 which may be of any conventional design. Amplitude separator 4 may be, for example, a comparator whose reference voltage on input line 16 is approximately equal to the 50-percent amplitude level of the clamped sync pulse. Thus, the comparator output will be only that portion of the dc-restored composite video signal between the 50-percent point and the tip of sync; thus, the video signal will be removed. Those desiring more detailed information concerning the operation of dc restorers, amplitude separators and sync separators in general are referred to the circuit concept book &#34;Televison Waveform Processing Circuits&#34;, by G. A. Eastman, copyright 1968 by Tektronix, Inc. which is incorporated herein by reference. 
     When there is a sync pulse output from amplitude separator 4, monostable multivibrator 8 will stay in the triggered condition. If, however, a large negative voltage spike enters the cicruit and drives the output of dc restorer 2 below the operating threshold of amplitude separator 4, there will be no pulse output therefrom. When there is no pulse output from amplitude separator 4 for more than one horizontal line period, monostable multivibrator 8 will time out. The output from monostable multivibrator 8 is coupled to variable current source 6 and increases the current output thereof when monostable multivibrator 8 is timed out. This increased current will decrease the time required for the sync separator to recover from the missed sync pulse. As soon as the output of dc restorer 2 has recovered and the input signal is at the correct level to turn on amplitude separator 4, monostable multivibrator 8 is triggered and the dc restored current returned to normal. 
     Shown in FIG. 2 is a schematic representation of a sync separator circuit according to the present invention. Before considering the overall operation of the circuit, provided below are component values that have proven useful in one embodiment of the invention. We do not, however, wish to be limited to this or any other particular set of components. 
     
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Transistors 20, 30, 40, 50 and 60                                         
                         CA3096                                           
Transistors 90, 120, 130 and 150                                          
                         MPS6523                                          
Transistors 110, 140 and 160                                              
                         MPS6521                                          
Diodes 185 and 195       1N4148                                           
Capacitor 100            0.047 μf                                      
Capacitor 180            0.022 μf                                      
Potentiometer 80         50 k Ω                                     
Potentiometer 170        10 k Ω                                     
Resistor 70              1 M Ω                                      
Resistor 71              22 k Ω                                     
Resistor 85              33 k Ω                                     
Resistor 165             470 Ω                                      
Resistor 190             680 Ω                                      
Resistor 210             510 Ω                                      
Resistor 175             62 k Ω                                     
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     The incoming composite video signal enters the circuit on input line 10 and is buffered by emitter follower NPN transistor 110. From the emitter of transistor 110 the video signal is coupled to a dc-restorer circuit comprising NPN transistor 60, PNP transistor 90 and capacitor 100. Transistors 60 and 90 are connected so as to function as an extremely square-cornered clamping diode. During the sync interval of the composite video, a dc restoration voltage is developed across capacitor 100. During the video interval of the composite video signal, a current source 6 provides current to charge capacitor 100 thereby replacing charge removed during the sync interval of the composite video signal. In this embodiment, current source 6 comprises PNP transistor 20, PNP transistor 30, NPN transistor 40, NPN transistor 50 and resistor 70. Transistors 20 and 30 are used as a voltage-level shifter for the conventional current mirror current source of transistors 50 and 60. U.S. Pat. No. 3,939,434 granted to P. S. Crosby, Feb. 17, 1976, which is incorporated herein by reference, discloses an alternate current mirror that may be used. The initial rundown current for capacitor 100 is provided by resistor 70 through the level shifter and current mirror. Additional current is supplied to capacitor 100, through resistor 71, by an external voltage source designated as V REF  in FIG. 2. This may be a dc voltage that represents the average amplitude of the sync pulse. This reference voltage causes the rundown current on the signal fed to capacitor 100 to be a constant percentage of the sync pulse amplitude, thus insuring a constant clamping action independent of the sync amplitude over a wide range. The actual dc level of the sync tip may be adjusted over a small range by using potentiometer 80 to compensate for any offset error introduced by amplitude separator 4. 
     The sync-tip clamped video is buffered by PNP emitter follower transistor 120 and fed to amplitude separator 4. In this embodiment, amplitude separator 4 comprises a pair of differentially coupled PNP transistors (130 and 150) and NPN transistor 140. Initially, the dc voltage at the base of transistor 150 is at ground and potentiometer 80 is set so that the negative tip of the sync pulse just turns on transistor 130. Therefore only the tip of the sync pulse will appear at the collector of transistor 130. After startup, the voltage at the base of transistor 150 will rise to approximately 50 percent of the average amplitude of the sync pulse. This occurs because the previously-mentioned V REF  voltage is connected to the base of transistor 150 through the voltage divider of resistors 190 and 210. Placing the base of transistor 150 at this dc voltage, rather than at ground, causes the sync pulse to be picked off the clamped video at the 50-percent level. This is the well known technique of 50-percent sync tracking. NPN transistor 140 has its base connected to the collector of transistor 150 and to a negative voltage supply through potentiometer 170. The emitter of transistor 150 is connected to the same negative voltage supply and the collector thereof is connected to the collector of transistor 130. Potentiometer 170 allows regulation of stored charge removal from transistor 140 and may thereby be used to delay the leading edge of the separated sync pulse at the collector of transistor 140. 
     The function of retriggerable monostable multivibrator 8 is implemented, in this embodiment, by NPN transistor 160, diodes 185 and 195, capacitor 180 and resistor 175. When impulse noise is not present on the incoming video and the separated sync pulse are present at the collector of transistor 130, transistor 160 performs a buffering function to isolate the sync separator from the next processing stage. During each sync pulse, transistor 160 draws current through resistor 165. This current appears at the collector of transistor 160 and charges capacitor 180 until diode 185 turns on. Between sync pulses, resistor 175 charges capacitor 180 in a positive direction. However, resistor 175 is chosen such that the charge on capacitor 180 will not cross the combined band gap of diode 185 and 195. Each time a sync pulse is passed by transistor 160, capacitor 180 is recharged to the threshold of diode 185. 
     When a negative noise spike enters the sync separator it is coupled to and causes capacitor 100 to charge to such a low voltage that the sync signal no longer crosses the threshold voltage at which transistor 130 normally turns on. Consequently, there is no sync pulse at the collector of transistor 130 and the base of transistor 160. Without a signal on the base of transistor 160, current from resistor 175 will charge capacitor 180 far enough to turn diode 195 on. Thus, the current from resistor 175 will flow through diode 195 to the emitter of transistor 30 in the level-shifting circuit of current source 6. The current is then mirrored back to dc-restorer circuit 2 where it increases the rundown current to capacitor 100 and thereby decreases the time required for the dc restorer to recover from the negative-going voltage spike. As soon as the dc restorer has recovered and the sync pulse at the base of transistor 130 has once again passed through the threshold voltage thereof, capacitor 180 is discharged by transistor 160. Therefore, the monostable multivibrator function is effectively set and will not time out until another sync pulse is missed. 
     While we have shown and described a preferred embodiment of our invention, it will be apparent to those skilled in the art that many changes and modifications may be made without departing from our invention in its broader aspects. We therefore intend the appended claims to cover all such changes and modifications.