Digital-analog converter for conversion of law A- encoded digital signals into analog signals
This is a continuation, of application Ser. No. 007,839, filed Mar. 26, 1987, now abandoned. 
    
    
     The present invention relates to digital-analog converters and refers more particularly to digital-analog converters of signals coded by standardized data compression according to a standard compression law called law A. 
     Traditional law A digital-analog converters are produced according to the following algorithm: 
     Segment 0 
     Output =(+/-). (G&#39;/32+0).(1)/128.VREF 
     Segment 1 to 7 
     Output=(+/-).(G&#39;/32+1).(G&#34;)/128.VREF 
     G&#39; and G&#34; being the gains of two successive decoding stages respectively, 
     where : 
     G&#39;=(1,3,5,7, . . . 29 or 31) 
     G&#34;=(1,2,4,8,. . . 32 or 64) 
     This algorithm is materialized by a three-stage processor operated by means of silicon circuits. 
     It comprises a sign generator, a step generator and a segment generator. 
     The segment generator receives the reference voltage allocated with a sign &#34;SREF&#34; and a processed signal &#34;AREF&#34; which is the signal from the step generator. 
     An error at the output of the step generator directly causes a distortion at the output of the segment generator. 
     Decoders of the type mentioned above are strongly dependent on the performance of the sign generator and that of the step generator (offset, limited amplifier gain, amplifier voltage offset, clock injection. . . ). 
     The invention aims to create a new digital-analog converter which is not affected by these problems and has other advantages over traditional digital-analog converters. 
     It also aims to produce a digital-analog converter which is designed to be associated with a speech synthesis device which is of simple construction, which has a reduced number of components, which is small in size and whose performance is improved. 
     Its object is therefore a digital-analog converter intended to convert into analog signals digital signals formed of sign bits, of step bits and of segment bits, particularly signals coded by data compression according to law A, the said converter comprising a sign generator, intended to receive the sign bit of the said digital signal, a step generator, connected to the output of the sign generator and intended to receive the step bits of the said digital signal and a segment generator connected to the step generator and intended to receive the segment bits of the said digital signal, characterized in that the segment generator is connected to the sign generator by means of the step generator only. 
    
    
     The invention will be better understood with the help of the following description, given solely by way of example and with reference to the appended drawings in which: 
     FIG. 1 is a block diagram of a traditional digitalanalog converter; 
     FIG. 2 is a block diagram of a digital-analog converter according to the invention; 
     FIG. 3 is a complete circuit diagram of the digitalanalog decoder according to the invention; and 
     FIG. 4 is a diagram showing the appearance of the clock and input signals of the circuit in FIG. 3. 
    
    
     As already mentioned, a traditional digital-analog converter of the type shown in FIG. 1 comprises a sign generator 1, which receives on it sinput a sign reference signal and which is connected at its output to the input of a step generator 2 as well as to an input of a segment generator 3 another input of which is connected to the output of the step generator 2. 
     It can be seen that an error at the output of the step generator 2 directly causes a distortion at the output of the segment generator 3. 
     In accordance with the present invention, another way of decoding law A, has been provided which depends upon the following algorithm: 
     OUTPUT=(+/-) . G&#39;. (1/64) . G&#34;. (1/64) . VREF 
     where : 
     G&#39;=(1,3,5,7 . . . 61 or 63) 
     G&#34;=(1,2,4,8 . . . 32 or 64) 
     This algorithm is translated into a circuit based on silicon components, having three stages, shown in FIG. 2. 
     This circuit comprises a sign generator 4 having one input intended to receive a reference signal and two outputs 5,6 on which appear two signals SREF 1  and SREF 2 . 
     The two outputs 5, 6 of the sign generator are applied to two corresponding inputs of a step generator 7 whose output is connected to an input of a segment generator 8. 
     In FIG. 3, the step generator and the segment generator of the circuit in FIG. 2 have been shown in detail. 
     The step generator 7 is essentially formed by an operational amplifier 10 whose positive input is earthed and whose negative input is connected to seven capacitors 11a to 11g whose terminals opposite the input of the amplifier 10 are connected to one of the outputs of the sign generator 4, either directly for capacitor 11a, or via one or more switches 12b to 12g, 13b to 13g, 14c to 14g and 15c to 15g depending on the capacitor concerned. 
     The values of the capacitors 11a to 11g are 7C, 2C, 4C, 8C, 16C and 32C respectively. The value of capacitor 24 can be adjusted in order to regulate the gain of the complete converter. In this example, this value is 100 C. 
     The sign generator 4 is formed by a simple switching circuit with one input 16 earthed and one input 17 at a reference voltage and two sign outputs 18, 19. Two switches 20 and 21 are connected between earth and outputs 18 and 19 respectively. Two other switches 22 and 23 are connected between the reference input 17 and outputs 18 and 19 respectively. 
     A capacitor 24 and a switch 25 are connected in parallel between the negative input and the output of the operational amplifier 10. 
     The segment generator 8 is formed by an operational amplifier 26 whose positive input is earthed and whose negative input is connected to the output of the amplifier 10 of the step generator via capacitors 27a to 27g. 
     Capacitor 27a is directly connected to the output of the amplifier 10, while the other capacitors are connected to the output of this amplifier via switches 28b to 28g respectively and are earthed via switches 29b to 29g respectively. 
     The negative input of amplifier 26 is connected to its output by means of a capacitor 30 and a switch 31 in parallel. 
     The values of capacitors 27a to 27g connecting the negative input of the second amplifier 26 to the output of the first amplifier 10 are C,C, 2C,4C, 8C,16C and 32C respectively and the value of capacitor 30 connecting the negative input of the second amplifier 26 to its output is 64C. 
     The output of amplifier 26 is connected to an output filter 32 by means of a switch 33. The input capacity of the filter serves as a sampler-blocker. This capacity is represented by capacitor Cin. 
     The operation of the circuit in FIG. 3 will now be descreased with reference to the diagram in FIG. 4. 
     The law A input code is applied at the start of the restoration phases of the step and segment generators 7 and 8 by operating those of the switches 12b to 15g of the step generator and of switches 28b to 29g of the segment generator which correspond to the code to be converted. This code remains stable throughout the cycle in accordance with the input code. The capacitors 11a to 11g and 21a to 27g of the first and second networks of switched capacitors of the step and segment generators 7 and 8 are charged according to the code applied to them by the previously mentioned switches. 
     The switches 12b to 15g, 25, 28b to 29g, 31 and 33 are formed by transistors connected to a logic formed from AND, NOR, OR and NAND gates (not shown) which receives the code to be converted and which selects the elements of the said code for the purpose of controlling the charging of the corresponding capacitors. 
     The input code to be processed is an eight-bit word (sign +7 bits). 
     For the purpose of simplification, the coding of step or of a segment is here considered to be a simple binary coding in four bits for the steps and 3 bits for the segments. 
     For example, step 10 is simply coded 1010 and segment 3 is simply coded 011. 
     Input code =(SIGN,SEGMENT, STEP) 
     SIGN : Coded by one bit, SGN 
     SEGMENT : Coded by 3 bits, CH2, CH1 and CH0 
     STEP : Coded by 4 bits, ST3, ST2, ST1, and ST0 
     
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(OR CH2,CH1,CH0)                                                          
             ST3     ST2     ST1   ST0   G&#39;                               
0            0       0       0     0      1                               
0            0       0       0     1      3                               
0            0       0       1     0      5                               
0            0       0       1     1      7                               
0            0       1       0     0      9                               
0            0       1       0     1     11                               
0            0       1       1     0     13                               
0            0       1       1     1     15                               
0            1       0       0     0     17                               
1            1       1       1     1     63                               
CH2          CH1     CHO     G&#34;                                           
0            0       0       1                                            
0            0       1       1                                            
0            1       0       2                                            
0            1       1       4                                            
1            0       0       8                                            
1            0       1       16                                           
1            1       0       32                                           
1            1       1       64                                           
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     In this simplified diagram, neither the sign processor, nor the switches decoding the input sign are shown. 
     During the restoration phases RET 1  and RET 2 , the integration capacitors are short-circuited. 
     The selected input capaciters of the step generator 7 are connected to the reference voltage an are thus pre-charged to a voltage equal to that of the reference voltage reduced by the offset voltage of the first amplifier 10. The non-selected capacitors are earthed and are thus pre-charged to a voltage equal to the offset voltage of the first amplifier 10. 
     The selected input capacitors of the segment generator 8 are connected to the output of the step generator 7 and store the combined offset of the two amplifiers 10 and 20. 
     The non-selected capacitors are earthed and are thus pre-charged to a voltage equal to the offset voltage of the second amplifier 20. 
     The RET1 phase is ended when switch 25 short-circuiting the integration capacitor 24 connected in parallel with the switch 25 between the negative input and the output of the first amplifier 10 of the step generator 7 is open. The switching noises due to the clock signals are then stored in the selected input capacitors 27a to 27g of the segment generator 8. 
     The RET2 phase is ended when the switch 31 short-circuiting the integration capacitor 30 of the segment generator 8 is open. The switching noise due to the clock signals introduces a constant offset at the output of the segment generator 8. 
     During the decoding phase, the input capacitors of the step generator are earthed, the selected capacitors 11a to 11g of this generator transfer theri charge to the integration capacitor 24 and the non-selected capacitors remain grounded and, for this reason, do not transfer any charge. 
     The selected capacitors of the segment generator remain connected to the output of the step generator. 
     These capacitors controlled by this output transfer their charge to the integration capacitor 30 of the segment generator 8. The non-selected capacitors remain grounded and, for this reason, do not transfer any charge. 
     The offset of the first amplifier and the switching noise due to the clock signals during the opening of the switch 25 short-circuiting the integration capacitor 24 of the step generator 7 have no effect on the output of the system. A limited gain of the first amplifier would not cause any distortion at the output but would slightly reduce the overall gain. 
     The offset of the second amplifier 26 and the switching noise due to the clock signals on the opening of switch 31 short-circuiting the integration capacitor 30 of the segment generator 8 introduce a constant systematic offset at the output of the system with no distortion. 
     A limited gain of the second amplifier 26 would not cause any distortion at the output but would slightly reduce the gain of the system. 
     The suppression of interferences enables a considerable simplification of the sign generator of such a system. 
     The consequences of a clock injection are also greatly reduced by the fact that all the switches operate at a practically constant voltage. For the same reasons, the consequences of non-linear behavior of the component devices (switches, stray capacity of distributed lines. . . ) are also considerably reduced. 
     One advantage of the invention is that no following amplifier is used, as a device of this type has a reduced input dynamic range which limits the dynamic range of the system. 
     An example of conversion of a law A code using the circuit in FIG. 3 is given hereafter. 
     The control signals SGN, . . . G 1 , B2, . . . G2 are the results of decoding the eight-bit &#34;law A&#34; input code (sign, CH2, CH1, CHO, ST3, ST2, ST1, STO). 
     In FIG. 3, the signals applied to the various switches of the circuit have the following meanings. 
     
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             SIGN         → SGN                                    
             NOT (ST0)    → C1                                     
             NOT (ST1)    → D1                                     
             NOT (ST2)    → E1                                     
             NOT (ST3)    → F1                                     
       NOR(CH0,CH1,CH2)   → G1                                     
       NOR (CH1, CH2)     → B2                                     
NOR(CH2, AND (CH0,CH1)    → C2                                     
             NOT (CH2)    → D2                                     
NOR(AND(CH1,CH2), AND (CH0,CH1)                                           
                          → E2                                     
NAND(CH1,CH2)             → F2                                     
NAND(CH0,CH1,CH2)         → G2                                     
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     NSGN, NG, . . . , NG1, NG2 are the inverses of the signals SGN, C1, . . . , B2 . . . G2 respectively. 
     In this example, use is made of the considerable advantage offered by the structure according to the invention which enables the output voltage to be adjusted independently of the value of the reference input voltage without having to use an attenuation or special amplification stage. 
     In the present example, a capacitor is used which is formed by 100 unit capacitors in order to attenuate the output voltage (gain 0.80). 
     This can be achieved with the device of the invention and cannot be achieved with the equipment of the prior technique without an additional attenuator stage. 
     The output of this digital-analog converter can be used directly for example in a switched capacities output filter not described here. 
     The &#34;PH14&#34; phase is used to transfer the output voltage of the converter to this filter. 
     An analog-digital conversion is achieved using the data of the following table. 
     The output of this table must be divided by 4096 and multiplied by the value of the reference voltage. 
     
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Law A - Digital-analog conversion                                         
Segment                                                                   
Step  (0)    (1)    2    3    4    5     6     7                          
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0      1     33     66   132  264  528   1056  2112                       
1      3     35     70   140  280  560   1120  2240                       
2      5     37     74   148  296  592   1184  2368                       
3      7     39     78   156  312  624   1248  2496                       
4      9     41     82   164  328  656   1312  2624                       
5     11     43     86   172  344  388   1376  2752                       
6     13     45     90   180  360  720   1440  2880                       
7     15     47     94   188  376  752   1504  3008                       
8     17     49     98   196  392  784   1568  3136                       
9     19     51     102  204  408  816   1632  3264                       
10    21     53     106  212  424  848   1696  3392                       
11    23     55     110  220  440  880   1760  3520                       
12    25     57     114  228  456  912   1824  3648                       
13    27     59     118  236  472  944   1888  3776                       
14    29     61     122  244  488  976   1952  3904                       
15    31     63     126  252  504  1008  2016  4032                       
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     For example, if it is desired to decode the value corresponding to segment 3 and step 10, the value 212 must be delivered. 
     The corresponding analog voltage obtained by the circuit is therefore: 212/4096. VREF 
     where VREF is the reference voltage. 
     The device of the invention can also be applied to analog-digital conversion. 
     For this conversion, law A is slightly different. 
     The output of the following table must be divided by 4096 and multiplied by the value of the reference voltage. 
     
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Law A - Analog Conversion (sic)                                           
Segment                                                                   
Step  (0)    (1)    2    3    4    5     6     7                          
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0      0     32     64   128  256  512   1024  2048                       
1      2     34     68   136  272  544   1088  2176                       
2      4     36     72   144  288  576   1152  2304                       
3      6     38     76   152  304  608   1216  2432                       
4      8     40     80   160  320  640   1280  2560                       
5     10     42     84   168  336  672   1344  2688                       
6     12     44     88   176  352  704   1408  2816                       
7     14     46     92   184  368  736   1472  2944                       
8     16     48     96   192  384  768   1536  3072                       
9     18     50     100  200  400  800   1600  3200                       
10    20     52     104  208  416  832   1664  3328                       
11    22     54     108  216  432  864   1728  3456                       
12    24     56     112  224  448  896   1792  3584                       
13    26     58     116  232  464  928   1856  3712                       
14    28     60     120  240  480  960   1920  3840                       
15    30     62     124  248  496  992   1984  3968                       
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     According to a known technique, an analog-digital converter can be produced using a digital-analog converter, a comparator and a logic control circuit. 
     This converter must follow law A for the analog-digital conversion. 
     All of the coefficients G&#39; and G&#34; can be directly adapted to this law by considering that the value to be st up are also the product of two integers. 
     The converters shown in FIG. 3 is of reduced size as it requires: (in the case of a system gain equal to 1) 
     64 unit capacitors as input capacitors for the step generator; 
     64 unit capacitors as integration capacitors of the step generator; 
     64 unit capacitors as input capacitors of the segment generator; 
     64 unit capacitors as integration capacitors of the segment generator; instead of: 
     32 unit capacitors as input capacitors of the step generator; 
     32 unit capacitors as integration capacitors of the step generator; 
     128 unit capacitors as input capacitors of the segment generator; 
     128 unit capacitors as integration capacitors of the segment generator; 
     for a traditional architecture. 
     This reduced size of the capacitor network enables better speed performance and/or a reduced size of the amplifiers. 
     Another advantage of the arrangement of the invention is that the gain of the complete system can be adjusted during the design simply by regulating the value of the first or second integration capacitors or both of them. 
     The reference voltage of a circuit can thus be used without adjustment by a special stage. 
     In addition, the decoding of the input code is particularly simple and direct. 
     In comparison with the traditional arrangements, the number of switches is divided by two and the control logic is considerably simplified and reduced.