DE102012206976A1 - Switching converter for operating at least one LED - Google Patents
Switching converter for operating at least one LED Download PDF
DE102012206976A1
DE102012206976A1 DE102012206976A DE102012206976A DE102012206976A1 DE 102012206976 A1 DE102012206976 A1 DE 102012206976A1 DE 102012206976 A DE102012206976 A DE 102012206976A DE 102012206976 A DE102012206976 A DE 102012206976A DE 102012206976 A1 DE102012206976 A1 DE 102012206976A1
switching converter
DE102012206976A
DE102012206976B4 (en
Richard Dilger
Markus Heckmann
Arnulf Rupp
Markus Nordhausen
Osram GmbH
2012-04-26 Application filed by Osram GmbH filed Critical Osram GmbH
2012-04-26 Priority to DE102012206976.3A priority Critical patent/DE102012206976B4/en
2013-10-31 Publication of DE102012206976A1 publication Critical patent/DE102012206976A1/en
2014-09-25 Publication of DE102012206976B4 publication Critical patent/DE102012206976B4/en
244000171263 Ribes grossularia Species 0.000 claims abstract description 70
230000001808 coupling Effects 0.000 claims abstract description 8
238000010168 coupling process Methods 0.000 claims abstract description 8
238000005859 coupling reactions Methods 0.000 claims abstract description 8
230000003595 spectral Effects 0.000 claims abstract description 5
239000003990 capacitor Substances 0.000 claims description 51
238000004146 energy storage Methods 0.000 claims description 31
239000003985 ceramic capacitor Substances 0.000 claims description 22
230000000875 corresponding Effects 0.000 claims description 2
230000001105 regulatory Effects 0.000 abstract description 2
230000002123 temporal effects Effects 0.000 abstract description 2
238000010586 diagrams Methods 0.000 description 2
239000010752 BS 2869 Class D Substances 0.000 description 1
238000000605 extraction Methods 0.000 description 1
238000009499 grossing Methods 0.000 description 1
238000000844 transformation Methods 0.000 description 1
H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
H02M1/00—Details of apparatus for conversion
H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
H02M1/4208—Arrangements for improving power factor of AC input
H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
H05B—ELECTRIC HEATING; ELECTRIC LIGHTING NOT OTHERWISE PROVIDED FOR
H05B45/00—Circuit arrangements for operating light emitting diodes [LED]
H05B45/30—Driver circuits
H05B45/37—Converter circuits
H05B45/355—Power factor correction [PFC]; Reactive power compensation
Y02B70/126—
The invention relates to a switching converter for operating at least one LED, which has a longer service life. The switching converter (10) according to the invention comprises an input (E1, E2) for coupling to an AC voltage source, an output (A1, A2) for coupling to the at least one LED, an input reactance network (12) having an input connected to an output of a Rectifier (11) is coupled, wherein the Eingangsreaktanznetzwerk (12) comprises at least a first controllable electronic switch, a capacitive energy store (C1) which is coupled to the output of the Eingangsreaktanznetzwerks (12) and at least a first electronic control circuit, by means of which the switching converter (10) by appropriate control of the electronic switch at its input (E1, E2) to a desired value of the input current (IE (t)) is adjustable. The at least one first control circuit is designed in such a way that the switching converter (10) can be regulated at its input (E1, E2) to a desired value of the input current (IE (t)), the desired value having spectral components in its temporal course at a fundamental frequency of one Fundamental with a fundamental amplitude and at a frequency of at least one harmonic with a predetermined amplitude, wherein the at least one frequency is an integer multiple of the fundamental frequency.
The invention relates to a switching converter according to the preamble of patent claim 1.
To operate LEDs or LED strings with a mains voltage, usually a sinusoidal AC voltage with an effective value of 230V, current and voltage transformations are required to provide a current with a constant current as possible. In the prior art, circuit arrangements for operating LEDs are known which comprise two voltage transformers, wherein the first voltage converter, in particular an up-converter, and the second voltage converter are coupled to one another via an intermediate circuit capacitor. To rectify the AC voltage, a rectifier is connected in front of the first voltage converter. The first voltage converter is usually designed as a power factor correction circuit which synchronizes the input current and the input voltage, since in particular for powers of 25 W predetermined directives with regard to the mains current harmonics are to be fulfilled. With suitable dimensioning of the intermediate circuit capacitor, the power coupled into the second voltage converter via the intermediate circuit capacitor is almost constant over its course over time. As an intermediate circuit capacitor, an electrolytic capacitor with the largest possible capacity is preferably used to allow the best possible smoothing of the voltage and the power. The second voltage converter converts the voltage such that the LEDs coupled to the output of the voltage converter can be supplied with a current of the most constant possible current. In this case, the second voltage converter is generally designed as a step-down converter, since usually only a small voltage is required to operate an LED.
A disadvantage of such circuit arrangements is that the electrolytic capacitors required for this purpose have a relatively short service life, which reduces the life of the entire circuit arrangement.
Presentation of the invention
The object of the present invention is to provide a switching converter for operating at least one LED, which has a longer service life.
This object is achieved by a switching converter having the features of patent claim 1.
Particularly advantageous embodiments can be found in the dependent claims.
The switching converter according to the invention for operating at least one LED comprises an input having a first and a second input terminal for coupling to an AC voltage source, an output having a first and a second output terminal for coupling to the at least one LED, wherein an output variable can be provided at the output, and a rectifier having an input coupled to the input of the switching converter and an output. The switching converter further comprises an input reactance network having an input coupled to the output of the rectifier and an output, the input reactance network including at least a first controllable electronic switch. Furthermore, the switching converter has a capacitive energy store, which is coupled to the output of the Eingangsreaktanznetzwerks, and at least a first electronic control circuit, by means of which the switching converter is adjustable at its input to a desired value of the input current. In this case, the at least one first control circuit is designed such that the switching converter is controllable at its input to a desired value of the input current, wherein the desired value in its time course spectral components at a fundamental frequency of a fundamental with a fundamental amplitude and at least one frequency at least one harmonic with a predetermined amplitude, wherein the at least one frequency is an integer multiple of the fundamental frequency.
Such a design of the at least one first control circuit makes it possible to distort the input current harmonically. In this case, to achieve a desired harmonic distortion, the amplitudes of the harmonics can be specified. In this case, the amplitudes are preferably predetermined in such a way that a power which is fed from the input reactance network into the capacitive energy store is maximally uniform over its time course. Due to the harmonic distortion of the power less energy must be stored by the capacitive energy storage over half a period based on the period of the fundamental frequency. This makes it possible to design the capacitive energy storage with a smaller capacity than with an undistorted power input. This provides the opportunity to use as capacitive energy storage other capacitors with smaller capacity and longer life than the commonly used electrolytic capacitors. Thus, by using capacitors with smaller capacity and longer life, the life of the entire switching converter can be increased.
In an advantageous embodiment of the invention by means of the control circuit of the switching converter can be controlled to a time varying setpoint of the input current having spectral components at frequencies of several harmonics, each having a predetermined amplitude, wherein the frequencies are odd multiples of the fundamental frequency. By means of harmonics with the 3-fold, 5-fold, 7-fold, etc. Frequency of the fundamental frequency can be a power that is fed from the input reactance network in the capacitive energy storage, which is so harmonic distorted that their time course is maximally uniform ie that the variation in power from the time average of power is reduced in magnitude and in time over power factor corrected power, which is proportional to the square of a sinusoid, as is conventional in the art.
Furthermore, the amplitudes of the harmonics with frequencies up to 49 times the fundamental frequency can be specified.
Preferably, the input voltage is a sinusoidal AC voltage having a frequency, wherein the first control circuit is adapted to regulate the switching converter at its input to a desired value of the input current, wherein the desired value in its time course has a fundamental with the same frequency as that of the input voltage ,
In an advantageous embodiment of the invention, the first control circuit is adapted to regulate the switching converter at its input to a desired value of the input current, wherein the desired value in its time course has a fundamental vibration having no phase shift relative to the input voltage.
Furthermore, the harmonics of the input current may have any phase shift from the fundamental. In particular, the control circuit can also be designed to control the switching converter to an input current having harmonics with a predetermined phase shift relative to the fundamental. The phase shifts can be specified in such a way that the power delivered by the input reactance network is even more uniform in its time course, in particular so that the capacitance of the capacitive energy store can be further reduced.
In a further advantageous embodiment of the invention, the predeterminable amplitude of the at least one harmonic is less than or equal to the predetermined by a distortion standard for a mains current drainage amplitude. Since more stringent specifications with respect to the harmonic distortion, in particular with respect to the amplitudes of harmonics of the input current, are generally available from a power extraction from the power supply starting from about 25 W., it is provided to select the predefinable amplitudes still in the range of the permissible amplitudes, and preferably as close as possible at the maximum permissible amplitudes.
Furthermore, the switching converter may comprise an output reactance network having an input coupled to the capacitive energy storage, and an output for coupling to the at least one LED, the output reactance network comprising at least one second controllable electronic switch.
Preferably, the switching converter comprises at least one second control circuit, by means of which the switching converter can be regulated to an output variable.
Thus, the switching converter can be advantageously controlled by means of the second control circuit to a desired output voltage or a desired output current.
Preferably, the output is an output current, since the operation of LEDs as smooth as possible direct current is advantageous.
In a further advantageous embodiment of the invention, the at least one second control circuit is designed to regulate the switching converter to an output variable as a function of an instantaneous value of a tapped off across the capacitive energy storage voltage. Since the use of a capacitive energy store with a smaller capacity, the voltage tapped on the capacitive energy storage has a greater ripple, it is advantageous to form the second control circuit such that in the control of an output variable, in particular an output current of the temporal course of the capacitive energy storage can be tapped Tension is taken into account and not just their time average. Such a configuration of the second control circuit makes it possible to control, in spite of large ripples, the voltage applied to the output reactance network to an output current which is almost constant over time.
Furthermore, the input reactance network can be designed as an up-converter. About that In addition, the output reactance network may be configured as a down converter.
In an advantageous embodiment of the invention, the capacitive energy storage is a ceramic capacitor or a foil capacitor. Ceramic capacitors and film capacitors have a comparatively long life and are further designed for a large ripple of the applied voltage, while electrolytic capacitors are not designed for such a large ripple.
Moreover, it is advantageous if the capacitance of the ceramic capacitor or of the film capacitor is dimensioned such that a tapped on the ceramic capacitor or film capacitor voltage has a voltage ripple which is greater than 30% of the maximum value of the input voltage at the input of the switching converter. Thus, the same energy can be stored by increasing the DC link voltage, in particular by the greater ripple of the voltage across the capacitor, and with a ceramic or film capacitor smaller capacity, as with an electrolytic capacitor large capacity and small DC link voltage. Advantageously, the ripple of the voltage provided by the capacitor to the Ausgangsreaktanznetzwerk be greater than 100 volts, in particular greater than 200 volts. Usually, the voltage ripple in the prior art is about 60 V since an electrolytic capacitor can not tolerate a larger ripple of the voltage, thereby requiring a larger capacity. By using ceramic capacitors or film capacitors, which tolerate a significantly greater ripple, the same energy can be stored in the capacitor with smaller capacitance and larger DC link voltage.
Furthermore, it is advantageous if the capacitance of the ceramic capacitor or film capacitor is dimensioned such that the instantaneous value of the voltage that can be tapped off on the ceramic capacitor or film capacitor is greater than the instantaneous value of the voltage present at the input of the switching converter. This ensures that the system of input reactance network, control circuit and capacitive energy storage in conjunction with the switching actions of at least one active switch the task of real-time control of the switching converter to its input current is justified and that the system is stable and not given to its by the switching converter principle Limits are encountered.
Further advantages, features and details of the invention will become apparent from the following description of preferred embodiments and from the drawings.
In the following, the invention will be explained in more detail with reference to exemplary embodiments. The figures show:
1 a schematic representation of a switching converter according to an embodiment of the invention;
2 a schematic representation of a measurement diagram of the tapable capacitor capacitor voltage and provided at the output of the switching converter output current according to an embodiment of the invention;
3 a graphical representation of an output from an input reactance network to a capacitor power without harmonic distortion;
4a a graphical representation of a harmonic distortion input current according to an embodiment of the invention;
4b a graphical representation of the input reactance network according to the current from 4a harmonically distorted output power according to an embodiment of the invention;
5a a graphical representation of another harmonic distortion input current according to an embodiment of the invention; and
5b a graphical representation of the input reactance network according to the current from 5a harmonic distorted power delivered according to an embodiment of the invention.
Preferred embodiment of the invention
1 shows a schematic representation of a switching converter 10 according to an embodiment of the invention. This includes an input reactance network 12 , via a capacitive energy storage C1 with an output reactance network 13 is coupled. At input E1, E2 of the switching converter 10 a sinusoidal alternating voltage can be applied, in particular with 230 V rms voltage, which is provided by a rectifier 11 is rectified. The output reactance network 13 can be designed as a down-converter, in particular as a buck converter, so that a suitable for the operation of at least one LED output voltage U A at the output A1, A2 of the Switching converter can be provided. The input reactance network 12 can be designed as a boost converter, in particular as a boost converter, whereby the voltage can be increased, so that the tapped off at the capacitive energy storage C1 voltage U K is greater than the voltage applied to the input E1, E2 input voltage U E. Furthermore, the capacitive energy storage C1 is dimensioned such that the periodically varying from the Eingangsreaktanznetzwerk 12 taken power P (t) by energy storage in the capacitive energy storage C1 as temporally constant as possible power P 0 in the Ausgangsreaktanznetzwerk 13 can be coupled. Furthermore, the switching converter 10 comprise an electronic control circuit, by means of which the switching converter 10 to a desired value of the input current I E (t) is controllable. By appropriate control of an electronic switch by a drive circuit 14 the input current I E (t) is adjustable so that it has a fundamental of the same frequency as that of the input voltage U E and harmonics with integer multiples, in particular odd multiples, this frequency and predetermined amplitude. Due to this harmonic distortion of the input current I E (t) and thus also the Eingansreaktanznetzwerk 12 power P (t), the deviation of the power P (t) from the time average of the power P 0 in the amount can be reduced in the time average over a power P (t), which is proportional to the square of a sine wave. It can be excellently accomplished by this embodiment of the invention that less energy E has to be stored by the capacitive energy store C1 during half a period T / 2 with respect to the period T of the basic shrinkage, and the capacitive energy store C1 can be designed with a much smaller capacitance. As a capacitive energy storage C1, for example, a ceramic capacitor or film capacitor with a smaller capacitance C can be used as usual in the prior art, which show a variety of advantages over the commonly used electrolytic capacitors. Advantageously, ceramic and film capacitors are designed for a much greater voltage ripple ΔU, which provides the possibility of further reducing the capacitance of the ceramic capacitor or film capacitor by increasing the intermediate circuit voltage. This is due to the fact that the energy E, which can be stored by the capacitive energy storage C1, according to E = 0.5 C1 U K 2 depends on the one hand by the capacitance of the capacitive energy storage C1 and on the other by the voltage applied to the capacitive energy storage C1 voltage U K. Correspondingly, the same energy E can be stored with a smaller capacitance of the capacitive energy store C1 and, at the same time, a corresponding increase in the intermediate circuit voltage, as with a capacitive energy store C1 of greater capacitance and smaller intermediate circuit voltage. Another very important aspect is moreover that a ceramic capacitor or film capacitor has a much longer life than an electrolytic capacitor, which increases the life and reliability of the entire switching converter 10 increases, since the capacitive energy storage C1 is the life-determining element.
When using a ceramic capacitor or film capacitor with a small capacitance C, that of the capacitive energy storage C1 to the Ausgangsreaktanznetzwerk 13 provided capacitor voltage U K on a correspondingly larger voltage ripple .DELTA.U on. Accordingly, the output reactance network is 13 designed to compensate for such a voltage ripple .DELTA.U. For this purpose, a second control circuit can be provided which has a virtually constant output current I A at the output A1, A2 of the circuit arrangement 10 provides. For example, the output reactance network may include an active switch, in particular a controllable electronic switch. The first and second control circuit can also be designed as a single control circuit, in particular, this can be designed such that two different and mutually independent control tasks can be solved by this one control circuit. Furthermore, the possibility is provided of the input and output reactance network 12 . 13 form together as Cuk converter, in particular, the control of an input current I E (t) and an output current I A of the switching converter 10 by driving only a controllable electronic switch by means of the drive circuit 14 respectively. Another very advantageous possibility is the regulation of the switching converter 10 to realize an input current I E (t) and an output current I A by two controllable electronic switches, wherein preferably the input and Ausgangsreaktanznetzwerk 12 . 13 each comprise an active switch. These two switches can also be controlled by the drive circuit 14 be controlled. In accordance with a preferred embodiment of the invention, the triggering of the second switch can be effected as a function of the voltage U K which can be tapped on the capacitive energy store C1, not only as a function of the time average of this voltage U K , as is usual in the prior art, but also taking into account the time profile of the voltage U K , ie, as a function of an instantaneous value of the capacitive energy storage C1 tapped voltage U K. This particularly advantageous embodiment makes it possible to provide an output current I A which has a current ripple ΔI which is less than 10% of the maximum value of the output current I A.
In addition, can be provided as a further embodiment variant to form the boost converter as a power factor correction circuit, in particular so that a distortion standard is maintained with respect to the system current drain. In addition, it is particularly noteworthy that the efficiency of such a switching converter 10 is at least 80% -86%, in particular also what corresponds to an efficiency common in the prior art. This is remarkable insofar as, in spite of the larger voltage ripple ΔU, no significant losses occur due to additional loading of the circuit components, in particular of semiconductor elements. This is due, inter alia, to a further advantage of using a ceramic capacitor or a film capacitor, as there are fewer losses due to the smaller capacitance and the smaller resistor on a ceramic capacitor or film capacitor, the possibility of using a smaller capacity only by the invention described Measures is provided.
To illustrate how the use of a small capacitance ceramic capacitor as a DC link capacitor affects 2 a measurement diagram of the time course of the capacitive energy storage device provided by the capacitive capacitor C1 U K and the output of the reactance network 13 provided output current I A of a switching converter 10 illustrated according to an embodiment of the invention. Furthermore, in 2 at the entrance of the input reactance network 12 , which is designed as a boost converter, in particular as a power factor correction circuit, applied rectified rectified AC voltage U G in its time course. In this example, the input E1, E2 of the switching converter has 10 applied input voltage U E As can be seen, a frequency of 50 Hz., has the capacitor voltage U K of the capacitive energy storage means C1 a very large voltage ripple .DELTA.U of about 300 V, which is more than 90% of the maximum value of the applied to the input E1, E2 Input voltage U E is. This is made possible only by the use of a ceramic capacitor or film capacitor as a DC link capacitor, since the commonly used electrolytic capacitors are not designed for such a large voltage ripple. Furthermore, the output current I A of the switching converter 10 shown in its time course. As can be seen, the output reactance network 13 , In particular, the second control circuit, the large voltage ripple .DELTA.U compensate relatively well, so that the output current I A only a small current ripple .DELTA.I of about 40 mA, which corresponds to about 10% of the maximum value of the output current I A. This is made possible only by the fact that the control circuit is designed to regulate the output current I A taking into account the instantaneous instantaneous value of the capacitor voltage U K which can be tapped on the capacitor, thereby making it possible to produce a relatively constant output current I A , eg for operating LEDs. provide.
3 Figure 4 is a graphical representation of one of an input reactance network 12 output power P (t) without harmonic distortion. The time profile of the power P (t) corresponds to P (t) = 2P 0 sin 2 (ωt), which can be accomplished by forming the input reactance network as a power correction circuit, as is common in the prior art. The into the output reactance network 13 to be coupled average power is P 0 . To provide as constant a power as possible in the output reactance network 13 To be able to couple in, an energy E has to be stored by the capacitive energy store C1 over half an oscillation period T / 2, which energy can be stored in the hatched areas in 3 equivalent.
According to one embodiment of the invention, it is now provided to be able to reduce the capacitance of the capacitive energy storage C1 by the first control circuit being designed to control the input current I E (t) and thus that of the input reactance network 12 delivered power P (t) harmonic distort. Such distorted input currents I E (t) and powers P (t) are in the 4a to 5b shown.
4a shows a graphical representation of a harmonic distortion input current I E (t). The associated harmonic distorted power P (t) is in 4b shown. In this example, the middle one is in the output reactance network 13 power P 0 25 W to be coupled in the case of a sinusoidal alternating voltage with an effective value of 230 V as the input voltage U E. The energy E to be stored by the capacitive energy store C1 is in turn represented by the hatched areas. Due to the harmonic distortion, these surfaces, that is to say the energy E to be stored by the capacitive energy store C1, are much smaller than those in FIG 3 represented undistorted power P (t). In this example, the input current I E (t) was distorted by appropriate design of the first control circuit so that the provisions of Class C of the mains current distortion standard with respect to the amplitude components of the higher harmonics are still met. In particular, the predeterminable amplitudes of the harmonics were chosen such that they correspond to the maximum permissible amplitudes of this mains current distortion standard, and furthermore, only the amplitudes up to the 11th harmonic were predetermined. Furthermore, the harmonics in this example have no phase shift with respect to the fundamental of the input current I E (t). The switching converter according to the invention 10 However, particularly advantageously provides additionally the possibility of the input current I E (t) of the switching converter 10 to regulate such that the harmonics have a phase shift from each other and also with respect to the fundamental. Thus, in an especially clever way, these likewise predefinable phase shifts can be used to control the input current I E (t) and thus also that of the input reactance network 12 delivered power P (t) to modify such that the capacitive energy storage C1 can be further reduced in size.
5a shows a graphical representation of another harmonic distortion current I E (t) and 5b a graphical representation of the input reactance network 12 in accordance with the input current I E (t) 5a harmonic distorted, delivered power P (t). In this example, the middle one is in the output reactance network 13 power P 0 to be coupled in turn 25 W at a sinusoidal alternating voltage with an effective value of 230 V as the input voltage U E. In this case, the input current I E (t) was distorted by correspondingly predetermined amplitudes by means of the first control circuit so that the provisions of class D of the mains current distortion standard with respect to the amplitude components of the higher harmonics are still met. Here, too, the hatched areas correspond to the energy E to be stored by the capacitive energy store C1. As can be seen, the energy E to be stored can be further reduced by a stronger harmonic distortion. In particular, by a harmonic distortion, a reduction of the required capacitance of the capacitive energy storage C1 by about 41% at a distortion according to 4a and 4b , and about 60% with a distortion according to 5a and 5b be achieved with respect to an undistorted signal.
Overall, such a switching converter for operating at least one LED is provided, which makes it possible to reduce the capacitance of the capacitive energy storage by a first control circuit is designed to distort an input current harmonically, so that reduces the energy to be stored by the capacitive energy storage. By the thus given particularly advantageous possibility of using ceramic capacitors or film capacitors, which are designed for a larger voltage ripple, the capacitance of the capacitive energy storage can be additionally reduced while increasing the DC link voltage. In addition, an essential advantage of ceramic capacitors and film capacitors that they have a much longer life and are much more resistant to temperature than electrolytic capacitors, which in addition still an increase in the maximum operating temperature of the switching converter can be achieved.
Switching converter ( 10 ) for operating at least one LED, comprising: - an input (E1, E2) having a first and a second input terminal for coupling to an AC voltage source; - An output (A1, A2) having a first and a second output terminal for coupling to the at least one LED, wherein at the output (A1, A2), an output variable can be provided; A rectifier ( 11 ) with an input connected to the input (E1, E2) of the switching converter ( 10 ) and an output; An input reactance network ( 12 ) with an input connected to the output of the rectifier ( 11 ) and an output, wherein the input reactance network ( 12 ) comprises at least a first controllable electronic switch; A capacitive energy store (C1) connected to the output of the input reactance network (C1) 12 ) is coupled; At least one first electronic control circuit, by means of which the switching converter ( 10 ) is controlled by a corresponding control of the electronic switch at its input (E1, E2) to a desired value of the input current (I E (t)); characterized in that the at least one first control circuit is designed such that the switching converter ( 10 ) at its input (E1, E2) to a desired value of the input current (I E (t)) is controllable, wherein the desired value in its time course spectral components at a fundamental frequency of a fundamental with a fundamental amplitude and at a frequency of at least one harmonic with a predeterminable amplitude, wherein the at least one frequency is an integer multiple of the fundamental frequency.
Switching converter ( 10 ) according to claim 1, characterized in that by means of the control circuit of the switching converter ( 10 ) is variable to a time varying setpoint value of the input current (I E (t)), the spectral components having at frequencies of several harmonics, each having a predetermined amplitude, wherein the frequencies are odd multiples of the fundamental frequency.
Switching converter ( 10 ) according to claim 2, characterized in that the amplitudes of the harmonics with frequencies up to 49 times the fundamental frequency can be predetermined.
Switching converter ( 10 ) according to one of the preceding claims, characterized in that the input voltage (U E ) is a sinusoidal alternating voltage with a frequency, wherein the first control circuit is designed to connect the switching converter ( 10 ) at its input (E1, E2) to a desired value of the input current (I E (t)) to regulate, wherein the desired value in its time course has a fundamental with the same frequency as that of the input voltage U E.
Switching converter ( 10 ) according to any one of the preceding claims, characterized in that the first control circuit is adapted to the switching converter ( 10 ) at its input (E1, E2) to a desired value of the input current (I E (t)) to regulate, wherein the desired value in its time course has a fundamental vibration, which has no phase shift relative to the input voltage U E.
Switching converter ( 10 ) according to any one of the preceding claims, characterized in that the predeterminable amplitude of the at least one harmonic is less than or equal to the predetermined by a distortion standard for the mains current consumption amplitude.
Switching converter ( 10 ) according to one of the preceding claims, characterized in that the switching converter ( 10 ) an output reactance network ( 13 ) having an input coupled to the capacitive energy storage (C1), and an output (A1, A2) for coupling to the at least one LED, the output reactance network ( 13 ) comprises at least one second controllable electronic switch.
Switching converter ( 10 ) according to one of the preceding claims, characterized in that the switching converter ( 10 ) comprises at least one second control circuit, by means of which the switching converter ( 10 ) is adjustable to an output variable.
Switching converter ( 10 ) according to claim 8, characterized in that the output variable is an output current (I A ).
Switching converter ( 10 ) according to one of claims 8 or 9, characterized in that the at least one second control circuit is adapted to the switching converter ( 10 ) to control an output variable as a function of an instantaneous value of a capacitive energy store (C1) tapped voltage (U K ).
Switching converter ( 10 ) according to any one of the preceding claims, characterized in that the input reactance network ( 12 ) is designed as an up-converter.
Switching converter ( 10 ) according to one of claims 7 to 11, characterized in that the output reactance network ( 13 ) is designed as a down converter.
Switching converter ( 10 ) according to one of the preceding claims, characterized in that the capacitive energy store (C1) is a ceramic capacitor or film capacitor.
Switching converter ( 10 ) according to claim 13, characterized in that the capacitance of the ceramic capacitor or film capacitor is dimensioned such that a tapable to the ceramic capacitor or film capacitor voltage (U K ) has a voltage ripple (.DELTA.U) which is greater than 30% of the maximum value of the input ( E1, E2) of the switching converter ( 10 ) applied input voltage (U E ).
Switching converter ( 10 ) according to one of claims 13 or 14, characterized in that the capacitance of the ceramic capacitor or film capacitor is dimensioned such that the instantaneous value of the tapped on the ceramic capacitor voltage (U K ) is greater than the instantaneous value of the input (E1, E2) of the switching converter ( 10 ) voltage applied (U E ).
DE102012206976.3A 2012-04-26 2012-04-26 Switching converter for operating at least one LED Active DE102012206976B4 (en)
DE102012206976.3A DE102012206976B4 (en) 2012-04-26 2012-04-26 Switching converter for operating at least one LED
PCT/EP2013/058776 WO2013160462A1 (en) 2012-04-26 2013-04-26 Switching converter for operating at least one led
DE102012206976A1 true DE102012206976A1 (en) 2013-10-31
DE102012206976B4 DE102012206976B4 (en) 2014-09-25
DE102012206976.3A Active DE102012206976B4 (en) 2012-04-26 2012-04-26 Switching converter for operating at least one LED
DE (1) DE102012206976B4 (en)
DE102014205469A1 (en) * 2014-03-24 2015-09-24 Osram Gmbh Circuit arrangement and method for operating semiconductor light sources
US10159123B2 (en) 2014-03-24 2018-12-18 Osram Gmbh Circuit arrangement and method for operating semiconductor light sources
DE19713814A1 (en) * 1997-04-03 1998-10-15 Siemens Ag Switching power supply
EP2315497A1 (en) * 2009-10-09 2011-04-27 Nxp B.V. An LED driver circuit having headroom/dropout voltage control and power factor correction
DE102010039154A1 (en) * 2010-08-10 2012-02-16 Tridonic Gmbh & Co. Kg Modulation of a PFC in DC mode
ES2442522T3 (en) * 2007-06-27 2014-02-12 Koninklijke Philips N.V. Powering a signal to a light source
2012-04-26 DE DE102012206976.3A patent/DE102012206976B4/en active Active
2013-04-26 WO PCT/EP2013/058776 patent/WO2013160462A1/en active Application Filing
DE102012206976B4 (en) 2014-09-25
Wang et al. 2013 Use of a series voltage compensator for reduction of the DC-link capacitance in a capacitor-supported system
US8817509B2 (en) 2014-08-26 High frequency power supply device
US8493757B2 (en) 2013-07-23 AC/DC converter with a PFC and a DC/DC converter
CA2660033C (en) 2015-12-22 Power supply control for power generator
ES2350945T3 (en) 2011-01-28 Power factor correction device for speed variator.
JP6080345B2 (en) 2017-02-15 Switching power supply and AC waveform generation method in switching power supply
US8861236B2 (en) 2014-10-14 Switching power supply with self-optimizing efficiency
US8525495B2 (en) 2013-09-03 Input current generator for buck-boost circuit control
JP6075462B2 (en) 2017-02-08 Power factor correction circuit
JP3795863B2 (en) 2006-07-12 Single-stage PFC + ballast control circuit / general-purpose power converter
TWI291804B (en) 2007-12-21 Switching power supply circuit and inverter
US20040202012A1 (en) 2004-10-14 Regulated AC to DC converter for aerospace applications
RU2427954C2 (en) 2011-08-27 Feed circuit and device containing feed circuit
CN101164383B (en) 2012-07-04 Parameterizable digital pfc
US8363433B2 (en) 2013-01-29 Hybrid conditioner for a power system
JP2010140675A (en) 2010-06-24 Power supply device
US7330366B2 (en) 2008-02-12 DC-AC converter
CA2856221A1 (en) 2013-05-23 Led power source with over-voltage protection
US7745970B2 (en) 2010-06-29 Circuitry for supplying a load with an output current
WO2013056356A1 (en) 2013-04-25 Ripple cancellation converter with high power factor
US7613018B2 (en) 2009-11-03 Apparatus and method for supplying DC power source
JP6588531B2 (en) 2019-10-09 Driver device and driving method
US10277067B2 (en) 2019-04-30 Power supply control
JP2007104872A (en) 2007-04-19 Power converter
JP4207824B2 (en) 2009-01-14 Switching power supply
2012-05-07 R012 Request for examination validly filed
2012-10-31 R016 Response to examination communication
2019-11-25 R079 Amendment of ipc main class
Free format text: PREVIOUS MAIN CLASS: H05B0037020000
Ipc: H05B0047100000